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caution: these devices are sensitive to electrostatic discharge. users should follow proper ic handling procedures. copyright ? harris corporation 1996 prism? and the prism? logo are trademarks of harris corporation 1 semiconductor simpli?ed block diagram rssi i in q in i out q out dpsk demod. pro- cessor dpsk mod. data to network ctrl processor 6-bit a/d 3-bit a/d 3-bit a/d cca spreader de-spreader inter- face pinout hsp3824 (tqfp) 1 2 3 4 5 6 7 8 32 31 30 29 28 27 26 25 24 23 22 21 20 19 18 17 9 10 11 12 13 14 15 16 33 34 35 36 37 38 39 40 41 42 43 44 45 46 47 48 rxclk rxd md_rdy rx_pe cca gnd mclk v dd reset antsel a/d_cal sd test_ck tx_pe txd txclk tx_rdy r/ w cs v dd gnd i in gnd v dd i out q out test7 test6 test5 v dd gnd test3 test2 test1 test0 test4 q in rssi gnd v refp v refn v dd gnd v dd v dd gnd as sclk hsp3824 direct sequence spread spectrum baseband processor features ? complete dsss baseband processor ? high data rate. . . . . . . . . . . . . . . . . . . . .up to 4 mbps ? processing gain . . . . . . . . . . . . . . . . . . . . . up to 12db ? programmable pn code . . . . . . . . . . . . up to 16 bits ? ultra small package . . . . . . . . . . . . . . . . . 7 x 7 x 1mm ? single supply operation (33mhz max) . . 2.7v to 5.5v ? single supply operation (44mhz max) . . 3.3v to 5.0v ? modulation method . . . . . . . . . . . . . dbpsk or dqpsk ? supports full or half duplex operations ? on-chip a/d converters for i/q data (3-bit, 44 msps) and rssi (6-bit, 2 msps) applications ? systems targeting ieee802.11 standard ? dsss pcmcia wireless transceiver ? spread spectrum wlan rf modems ? tdma packet protocol radios ? part 15 compliant radio links ? portable bar code scanners/pos terminal ? portable pda/notebook computer ? wireless digital audio ? wireless digital video ? pcn/wireless pbx preliminary march 1996 file number 4064.2 description the harris hsp3824 direct sequence (dsss) baseband pro- cessor is part of the prism? 2.4ghz radio chipset, and contains all the functions necessary for a full or half duplex packet base- band transceiver. the hsp3824 has on-board adcs for analog i and q inputs, for which the hfa3724 if qmodem is recommended. differential phase shift keying modulation schemes dbpsk and dqpsk, with optional data scrambling capability, are combined with a pro- grammable pn sequence of up to 16 bits. built-in ?exibility allows the hsp3824 to be con?gured through a general purpose control bus, for a wide range of applications. a receive signal strength indicator (rssi) monitoring function with on-board 6-bit 2 msps adc provides clear channel assessment (cca) to avoid data collisions and optimize network throughput. the hsp3824 is housed in a thin plastic quad ?at package (tqfp) suitable for pcmcia board applications. ordering information part no. temp. range pkg. type pkg. no. HSP3824VI -40 o c to +85 o c 48 lead tqfp q48.7x7 tm
2 hsp3824 list of contents typical application diagram. . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 3 pin description. . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 4 external interfaces . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 7 control port . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 7 tx port. . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 10 rx port . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 11 i/q adc interface. . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 11 adc calibration circuit and registers. . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 12 rssi adc interface . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 12 test port. . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 12 de?nitions . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 13 external agc control . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 13 power down modes . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 13 reset . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 14 transmitter description . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 14 header/packet description . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 15 pn generator description. . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 17 scrambler and data encoder description . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 17 modulator description . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 18 clear channel assessment (cca) and energy detect (ed) description . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 18 receiver description . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 20 acquisition description . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 20 two antenna acquisition . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 20 one antenna acquisition . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 21 acquisition signal quality parameters. . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 21 procedure to set acq. signal quality parameters (example) . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 21 pn correlator description . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 22 data demodulation and tracking description . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 22 procedure to set signal quality registers . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 22 data decoder and descrambler description . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 23 demodulator performance . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 23 overall eb/n0 versus ber performance. . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 23 clock offset tracking performance . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 24 carrier offset frequency performance . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 24 i/q amplitude imbalance . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 24 a default register con?guration . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 24 control registers . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 27 hsp3824 33mhz . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 37 hsp3824 . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 38 hsp3824 44mhz . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 39 test circuit . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 39 waveforms . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 40 thin plastic quad flatpack packages (tqfp) . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 41
3 hsp3824 typical application diagram quad if modulator rfpa hfa3925 hfa3724 dsss baseband processor data to mac ctrl hsp3824 tune/select hfa3524 0 o /90 o vco a/d a/d mac-phy interface 802.11 vco dual synthesizer hfa3624 rf/if converter a/d (file# 4067) (file# 4064) (file# 4062) (file# 4066) (file# 4132) prism? chip set file #4063 m u x m u x dpsk demod dpsk mod. de- spread spread q i hfa3424 (note) (file# 4131) typical transceiver application circuit using the hsp3824 note: required for systems targeting 802.11 speci?cations. cca rxi rxq rssi txi txq ? ? 2 for additional information on the prism? chip set, call (407) 724-7800 to access harris answerfax system. when prompted, key in the four-digit document number (file #) of the datasheets you wish to receive. the four-digit ?le numbers are shown in typical application diagram, and correspond to the appropriate circuit.
4 hsp3824 pin description name pin type i/o description v dd (analog) 10, 18, 20 power dc power supply 2.7v - 5.5v v dd (digital) 7, 21, 29, 42 power dc power supply 2.7v - 5.5v gnd (analog) 11, 15, 19 ground dc power supply 2.7v - 5.5v, ground. gnd (digital) 6, 22, 31, 41 ground dc power supply 2.7v - 5.5v, ground. v refn 17 i negative voltage reference for adcs (i and q) [relative to v refp ] v refp 16 i positive voltage reference for adcs (i, q and rssi) i in 12 i analog input to the internal 3-bit a/d of the in-phase received data. q in 13 i analog input to the internal 3-bit a/d of the quadrature received data. rssi 14 i receive signal strength indicator analog input. a/d_cal 26 o this signal is used internally as part of the i and q adc calibration circuit. when the adc calibration circuit is active, the voltage references of the adcs are adjusted to maintain the outputs of the adcs in their optimum range. a logic 1 on this pin indicates that one or both of the adc outputs are at their full scale value. this signal can be integrated externally as a control voltage for an external agc. tx_pe 2 i when active, the transmitter is con?gured to be operational, otherwise the transmitter is in standby mode. tx_pe is an input from the external media access controller (mac) or network processor to the hsp3824. the rising edge of tx_pe will start the internal transmit state machine and the falling edge will inhibit the state machine. tx_pe envelopes the transmit data. txd 3 i txd is an input, used to transfer serial data or preamble/header information bits from the mac or network processor to the hsp3824. the data is received serially with the lsb ?rst. the data is clocked in the hsp3824 at the falling edge of txclk. txclk 4 o txclk is a clock output used to receive the data on the txd from the mac or network processor to the hsp3824, synchronously. transmit data on the txd bus is clocked into the hsp3824 on the falling edge. the clocking edge is also programmable to be on either phase of the clock. the rate of the clock will be depending upon the modulation type and data rate that is programmed in the signalling ?eld of the header. tx_rdy 5 o when the hsp3824 is con?gured to generate the preamble and header information internally, tx_rdy is an output to the external network processor indicating that preamble and header information has been generated and that the hsp3824 is ready to receive the data packet from the network processor over the txd serial bus. the tx_rdy returns to the inactive state when the tx_pe goes inactive indicating the end of the data transmission. tx_rdy is an active high signal. this signal is meaningful only when the hsp3824 generates its own preamble. cca 32 o clear channel assessment (cca) is an output used to signal that the channel is clear to transmit. the cca algorithm is user programmable and makes its decision as a function of rssi, energy detect (ed), carrier sense (crs) and the cca watch dog timer. the cca algorithm and its programmable features are described in the data sheet. logic 0 = channel is clear to transmit. logic 1 = channel is not clear to transmit (busy). note: this polarity is programmable and can be inverted. rxd 35 o rxd is an output to the external network processor transferring demodulated header information and data in a serial format. the data is sent serially with the lsb ?rst. the data is frame aligned with md_rdy. rxclk 36 o rxclk is the clock output bit clock. this clock is used to transfer header information and data through the rxd serial bus to the network processor. this clock re?ects the bit rate in use.rxclk will be held to a logic 0 state during the acquisition process. rxclk becomes active when the hsp3824 enters in the data mode. this occurs once bit sync is declared and a valid signal quality estimate is made, when comparing the programmed signal quality thresholds.
5 hsp3824 md_rdy 34 o md_rdy is an output signal to the network processor, indicating a data packet is ready to be transferred to the processor. md_rdy is an active high signal and it envelopes the data transfer over the rxd serial bus. md_rdy returns to its inactive state when there is no more receiver data, when the programmable data length counter reaches its value or when the link has been interrupted. md_rdy remains inactive during preamble synchronization. rx_pe 33 i when active, receiver is con?gured to be operational, otherwise receiver is in standby mode. this is an active high input signal. antsel 27 o the antenna select signal changes state as the receiver switches from antenna to antenna during the acquisition process in the antenna diversity mode. sd 25 i/o sd is a serial bi-directional data bus which is used to transfer address and data to/from the internal registers. the bit ordering of an 8-bit word is msb ?rst. the ?rst 8 bits during transfers indicate the register address immediately followed by 8 more bits representing the data that needs to be written or read at that register. sclk 24 i sclk is the clock for the sd serial bus.the data on sd is clocked at the rising edge. sclk is an input clock and it is asynchronous to the internal master clock (mclk)the maximum rate of this clock is 10mhz or the master clock frequency, whichever is lower. as 23 i as is an address strobe used to envelope the address or the data on sd. logic 1 = envelopes the address bits. logic 0 = envelopes the data bits. r/ w8 ir/ w is an input to the hsp3824 used to change the direction of the sd bus when reading or writing data on the sd bus. r/ w must be set up prior to the rising edge of sclk. a high level indicates read while a low level is a write. cs 9 i cs is a chip select for the device to activate the serial control port.the cs doesnt impact any of the other interface ports and signals, i.e. the tx or rx ports and interface signals. this is an active low signal. when inactive sd, sclk, as and r/ w become dont care signals. test 0-7 37, 38, 39, 40, 43, 44, 45, 46 o this is a data port that can be programmed to bring out internal signals or data for monitoring. this data includes: correlator phase and magnitude, nco frequency offset estimate, and signal quality estimates. some of the discrete signals available include: carrier sense (crs), which becomes active when initial pn acquisition has been declared. energy detect (ed) which becomes active when the integrated rssi value exceeds the programmable threshold. both ed and crs are active high signals.these bits are primarily reserved by the manufacturer for testing. a further description of the test port is given at the appropriate section of this data sheet. test_ck 1 o this is the clock that is used in conjunction with the data that is being output from the test bus (test 0-7). reset 28 i master reset for device. when active tx and rx functions are disabled. if reset is kept low the hsp3824 goes into the power standby mode. reset does not alter any of the con?guration register values nor it presets any of the registers into default values. device requires programming upon power-up. reset must be inactive during programming of the device. mclk 30 i master clock for device. the maximum frequency of this clock is 44mhz. this is used internally to generate all other internal necessary clocks and is divided by 1, 2, 4, or 8 for the transceiver clocks. i out 48 o tx spread baseband i digital output data. data is output at the programmed chip rate. q out 47 o tx spread baseband q digital output data. data is output at the programmed chip rate. note: total of 48 pins; all pins are used. pin description (continued) name pin type i/o description
6 hsp3824 figure 1. dsss baseband processor preamble/header crc-16 rssi (14) 3-bit a/d i in (12) q in (13) 6-bit a/d ref 1.75v 0.25v v refp (16) v refn (17) vr3+ vr3- rssi ref 3 3 agc (26) mf correlator mf correlator pn code 11 to 16-bit symbol clock clear channel assessment/ (32) cca bit sync phase rotate psk demod lead /lag filter nco phase error rx_data descrambler (35) rxd tx_data scrambler (3) txd processor interface (36) rxclk pn generator i q i out (48) q out (47) pn code 11 to 16-bit z -1 xor diff decoder xor differential encoder b(t) b(t-1) d(t) d(t-1) latch xor xor chip rate clk mux clk for dqpsk i ch only for dbpsk analog de-spreader/acquisition dpsk demod spreader dpsk modulator and afc timing generator 8 8 signal quality and rssi sq and rssi threshold code (10, 18, 20) v dd (analog) (7, 21, 29, 42) v dd (digital) (11, 15, 19) gnd (analog) (6, 22, 31, 41) gnd (digital) (4) txclk (5) tx_rdy (2) tx_pe (33) rx_pe signal quality (34) md_rdy antsel (27) (24) sclk (25) sd (23) as (8) r/ w (9) cs serial control port transmit port receive port (30) mclk (28) reset test 0 (38) test 1 (37) (39) test 2 (40) test 3 (43) test 4 (44) test 5 (45) test 6 (46) test 7 test port test_ck (1) a/d reference level adjust. mag. / phase and timing distrib. signal quality z -1 mclk 8 2v (max) (min) 3-bit a/d 11 to 16-bit 11 to 16-bit and
7 hsp3824 external interfaces there are three primary digital interface ports for the hsp3824 that are used for con?guration and during normal operation of the device. these ports are: ? the tx port , which is used to accept the data that needs to be transmitted from the network processor. ? the rx port , which is used to output the received demod- ulated data to the network processor. ? the control port , which is used to con?gure, write and/or read the status of the internal hsp3824 registers. in addition to these primary digital interfaces the device includes a byte wide parallel test port which can be con?gured to output various internal signals and/or data (i.e. pn acquisi- tion indicator, correlator magnitude output etc.). the device can also be set into various power consumption modes by external control. the hsp3824 contains three analog to digital (a/d) converters. the analog interfaces to the hsp3824 include, the in phase (i) and quadrature (q) data component inputs, and the rf signal strength indicator input. a reference voltage divider is also required external to the device. figure 2. external interfaces txd txclk tx_rdy rxd rxc md_rdy c s sd sclk r/ w as i (analog) q (analog) rssi (analog) v refn v refp tx_pe rx_pe reset test tx_port rx_port control_port analog inputs a/d reference power down signals test port 8 hsp3824 control port the serial control port is used to serially write and read data to/ from the device. this serial port can operate up to a 10mhz rate or the maximum master clock rate of the device, mclk (whichever is lower). mclk must be running and reset inac- tive during programming. this port is used to program and to read all internal registers. the ?rst 8 bits always represent the address followed immediately by the 8 data bits for that register. the two lsbs of address are dont care. the serial transfers are accomplished through the serial data pin (sd). sd is a bidirectional serial data bus. an address strobe (as), chip select ( cs), and read/ wr ite (r/ w) are also required as handshake signals for this port. the clock used in conjunction with the address and data on sd is sclk. this clock is pro- vided by the external source and it is an input to the hsp3824. the timing relationships of these signals are illus- trated on figure 3 and 4. as is active high during the clock- ing of the address bits. r/ w is high when data is to be read, and low when it is to be written. cs must be active (low) dur- ing the entire data transfer cycle. cs selects the device. the serial control port operates asynchronously from the tx and rx ports and it can accomplish data transfers independent of the activity at the other digital or analog ports. cs does not effect the tx or rx operation of the device; impacting only the operation of the control port. the hsp3824 has 57 internal registers that can be con?gured through the control port. these registers are listed in the con?guration and con- trol internal register table. table 1 lists the con?guration reg- ister number, a brief name describing the register, and the hex address to access each of the registers. the type indi- cates whether the corresponding register is read only (r) or read/write (r/ w). some registers are two bytes wide as indicated on the table (high and low bytes). note: using falling edge sclk to generate address/control and capture read data. figure 3. control port read timing note: using falling edge sclk to generate address/control and data. figure 4. control port write timing 76543210765432107654 1 2 3 4 5 6 7 0 1 2 3 4 5 6 7 sclk sd as cs r/ w lsb data out msb msb address in first address bit in first databit out 76543210765432107654 1 2 3 4 5 6 7 0 1 2 3 4 5 6 7 0 sclk sd as cs r/ w lsb data in msb msb address in
8 hsp3824 table 1. configuration and control internal register list configuration register name type register address hex cr0 modem config. register a r/w 00 cr1 modem config. register b r/w 04 cr2 modem config. register c r/w 08 cr3 modem config. register d r/w 0c cr4 internal test register a r/w 10 cr5 internal test register b r/w 14 cr6 internal test register c r 18 cr7 modem status register a r 1c cr8 modem status register b r 20 cr9 i/o definition register r/w 24 cr10 rssi value register r 28 cr11 adc_cal_pos register r/w 2c cr12 adc_cal_neg register r/w 30 cr13 tx_spread sequence (high) r/w 34 cr14 tx_spread sequence (low) r/w 38 cr15 scramble_seed r/w 3c cr16 scramble_tap (rx and tx) r/w 40 cr17 cca_timer_th r/w 44 cr18 cca_cycle_th r/w 48 cr19 rssi_th r/w 4c cr20 rx_spread sequence (high) r/w 50 cr21 rx_spread sequence (low) r/w 54 cr22 rx_sq1_ acq (high) threshold r/w 58 cr23 rx-sq1_ acq (low) threshold r/w 5c cr24 rx-sq1_ acq (high) read r 60 cr25 rx-sq1_ acq (low) read r 64 cr26 rx-sq1_ data (high) threshold r/w 68 cr27 rx-sq1-sq1_ data (low) threshold r/w 6c cr28 rx-sq1_ data (high) read r 70 cr29 rx-sq1_ data (low) read r 74 cr30 rx-sq2_ acq (high) threshold r/w 78 cr31 rx-sq2- acq (low) threshold r/w 7c cr32 rx-sq2_ acq (high) read r 80
9 hsp3824 cr33 rx-sq2_ acq (low) read r 84 cr34 rx-sq2_data (high) threshold r/w 88 cr35 rx-sq2_data (low) threshold r/w 8c cr36 rx-sq2_data (high) read r 90 cr37 rx-sq2_data (low) read r 94 cr38 rx_sq_read; full protocol r 98 cr39 reserved (must load 00h) w 9c cr40 reserved (must load 00h) w a0 cr41 uw_time out_length r/w a4 cr42 sig_dbpsk field r/w a8 cr43 sig_dqpsk field r/w ac cr44 rx_ser_field r b0 cr45 rx_len field (high) r b4 cr46 rx_len field (low) r b8 cr47 rx_crc16 (high) r bc cr48 rx_crc16 (low) r c0 cr49 uw (high) r/w c4 cr50 uw (low) r/w c8 cr51 tx_ser_f r/w cc cr52 tx_len (high) r/w d0 cr53 tx_len (low) r/w d4 cr54 tx_crc16 (high) r d8 cr55 tx_crc16 (low) r dc cr56 tx_prem_len r/w e0 table 1. configuration and control internal register list (continued) configuration register name type register address hex
10 hsp3824 tx port the transmit data port accepts the data that needs to be transmitted serially from an external data source. the data is modulated and transmitted as soon as it is received from the external data source. the serial data is input to the hsp3824 through txd using the falling edge of txclk to clock it in the hsp3824. txclk is an output from the hsp3824. a timing scenario of the transmit signal hand- shakes and sequence is shown on timing diagram figures 5 and 6. the external processor initiates the transmit sequence by asserting tx_pe. tx_pe envelopes the transmit data packet on txd. the hsp3824 responds by generating txclk to input the serial data on txd. txclk will run until tx_pe goes back to its inactive state indicating the end of the data packet. there are two possible transmit scenarios. one scenario is when the hsp3824 internally generates the preamble and header information. during this mode the external source needs to provide only the data portion of the packet. the timing diagram of this mode is illustrated on fig- ure 6. when the hsp3824 generates the preamble inter- nally, assertion of tx_pe will initialize the generation of the preamble and header. tx_rdy, which is an output from the hsp3824, is used to indicate to the external processor that the preamble has been generated and the device is ready to receive the data packet to be transmitted from the external processor. the tx_rdy timing is programmable in case the external processor needs several clocks of advanced notice before actual data transmission is to begin. the second transmit scenario supported by the hsp3824 is when the preamble and header information are provided by the external data source. during this mode tx_rdy is not required as part of the tx handshake. the hsp3824 will immediately start transmitting the data available on txd upon assertion of tx_pe. the timing diagram of this tx sce- nario, where the preamble and header are generated exter- nal to the hsp3824, is illustrated on figure 5. one other signal that can be used for certain applications as part of the tx interface is the clear channel assessment (cca) signal which is an output from the hsp3824. the cca is programmable and it is described with more detail in the transmitter section of this document. cca provides the indication that the channel is clear of energy and the trans- mission will not be subject to collisions. cca can be moni- tored by the external processor to assist in deciding when to initiate transmissions. the cca indication can bypassed or ignored by the external processor. the state of the cca does not effect the transmit operation of the hsp3824. tx_pe alone will always initiate the transmit state indepen- dent of the state of cca. signals tx_rdy, tx_pe and txclk can be set individually, by programming con?gura- tion register (cr) 9, as either active high or active low sig- nals. the transmit port is completely independent from the opera- tion of the other interface ports including the rx port, there- fore supporting a full duplex mode. note: preamble/header and data is transmitted lsb ?rst tx_rdy is inactive logic 0 when generated externally. txd shown generated from rising edge txclk. figure 5. tx port timing (external preamble) note: preamble/header and data is transmitted lsb ?rst. txd shown generated from rising edge txclk. tx_rdy generated from falling edge. figure 6. tx port timing (internal preamble) txclk tx_pe txd preamble - header msb of last header field lsb data packet msb dummy bits to clear mod path preamble - header msb of last header field lsb data packet msb dummy bits to clear mod path txclk tx_pe txd tx_rdy
11 hsp3824 rx port the timing diagram figure 7 illustrates the relationships between the various signals of the rx port. the receive data port serially outputs the demodulated data from rxd. the data is output as soon as it is demodulated by the hsp3824. rx_pe must be at its active state throughout the receive operation. when rx_pe is inactive the device's receive functions, including acquisition, will be in a stand by mode. rxclk is an output from the hsp3824 and is the clock for the serial demodulated data on rxd. md_rdy is an output from the hsp3824 and it envelopes the valid data on rxd. the hsp3824 can be also programmed to ignore error detections during the ccitt - crc 16 check of the header ?elds. if programmed to ignore errors the device continues to output the demodulated data in its entirety regardless of the ccitt - crc 16 check result. this option is programmed through cr 2, bit 5. note that rxclk becomes active after acquisition, well before valid data begins to appear on rxd and md_rdy is asserted. md_rdy returns to its inactive state under the fol- lowing conditions: ? the number of data symbols, as de?ned by the length ?eld in the protocol, has been received and output through rxd in its entirety (normal condition). ? pn tracking is lost during demodulation. ? rx_pe is deactivated by the external controller. md_rdy can be con?gured through cr 9, bit 6 to be active low, or active high. energy detect (ed) pin 45 (test port), and carrier sense (crs) pin 46 (test port), are available outputs from the hsp3824 and can be useful signals for an effective rx interface design. use of these signals is optional. crs and ed are further described within this docu- ment. the receive port is completely independent from the operation of the other interface ports including the tx port, supporting therefore a full duplex mode. i/q adc interface the prism baseband processor chip (hsp3824) includes two 3-bit analog to digital converters (adcs) that sample the analog input from the if down converter. the i/q adc clock, mclk, samples at twice the chip rate. the maximum sampling rate is 44mhz (power supply: 3.3v to 5.0v) or 33mhz (power supply 2.7v to 5.5v). the interface speci?cations for the i and q adcs are listed on table 2 below. the voltages applied to pin 16,v refp and pin 17, v refn set the references for the internal i and q adc converters. in addition, v refp is also used to set the rssi adc converter reference. for a nominal 500mv p-p , the suggested v refp voltage is 1.75v, and the suggested v refn is 0.93v. v refn should never be less than 0.25v. since these adcs are intended to sample ac voltages, their inputs are biased internally and they should be capacitively coupled. the adc section includes a compensation (calibration) cir- cuit that automatically adjusts for temperature and compo- nent variations of the rf and if strips. the variations in gain of limiters, agc circuits, ?lters etc. can be compensated for up to 4db. without the compensation circuit, the adcs could see a loss of up to 1.5 bits of the 3 bits of quantization. the adc calibration circuit adjusts the adc reference volt- ages to maintain optimum quantization of the if input over this variation range. it works on the principle of setting the reference to insure that the signal is at full scale (saturation) a certain percentage of the time. note that this is not an agc and it will compensate only for slow variations in signal levels (several seconds). table 2. i, q, adc specifications parameter min typ max full scale input voltage (v p-p ) 0.25 0.50 1.0 input bandwidth (-0.5db) - 20mhz - input capacitance (pf) - 5 - input impedance (dc) 5k w -- fs (sampling frequency) - - 44mhz note: md_rdy active after crc16. figure 7. rx port timing rxclk rx_pe crs (test 7) md_rdy rxd processing lsb data msb preamble/header
12 hsp3824 the procedure for setting the adc references to accommo- date various input signal voltage levels is to set the reference voltages so that the adc calibration circuit is operating at half scale. this leaves the maximum amount of adjustment room for circuit tolerances. figure 8 illustrates the suggested interface con?guration for the adcs and the reference circuits. figure 8. interfaces adc calibration circuit and registers the adc compensation or calibration circuit is designed to optimize adc performance for the i and q inputs by main- taining the full 3-bit resolution of the outputs. there are two registers (cr 11 ad_cal_pos and cr 12 ad_cal_neg) that set the parameters for the internal i and q adc calibra- tion circuit. both i and q adc outputs are monitored by the adc calibra- tion circuit and if either has a full scale value, a 24-bit accu- mulator is incremented as de?ned by parameter ad_cal_pos. if neither has a full scale value, the accumu- lator is decremented as de?ned by parameter ad_cal_neg. a loop gain reduction is accomplished by using only the 5 msbs out of the 24 bits to drive a d/a converter that adjusts the adcs reference. the compensation adjustment is updated at 2khz rate for a 2 mbps operation. the adc cali- bration circuit is only intended to remove slow component variations. the ratio of the values from the two registers cr11 and cr12 set the probability that either the i or q adc converter will be at the saturation. the probability is set by (ad_cal_pos)/(ad_cal_neg). this also sets the levels so that operation with either noise or dpsk is approximately the same. it is assumed that the rf and if sections of the receiver have enough gain to cause limiting on thermal noise. this will keep the levels at the adc approximately same regardless of whether signal is present or not. the adc calibration voltage is automatically held during transmit in half duplex operation. the adc calibration circuit operation can be de?ned through cr 1, bits 1 and 0. table 3 illustrates the possible con?gurations. 0.01 m f 0.01 m f 3.9k 8.2k 9.1k i q 2v i in q in v refp v refn hsp3824 0.01 m f 0.01 m f rssi adc interface the receive signal strength indication (rssi) analog signal is input to a 6-bit adc, indicating 64 discrete levels of received signal strength. this adc measures a dc voltage, so its input must be dc coupled. pin 16 (v refp ) sets the reference for the rssi adc converter. v refp is common for the i and q and rssi adcs. the rssi signal is used as an input to the pro- grammable clear channel assessment algorithm of the hsp3824. the rssi adc output is stored in an 8-bit register (cr10) and it is updated at the symbol rate for access by the external processor to assist in network management. the interface speci?cations for the rssi adc are listed on table 4 below (v refp = 1.75v). test port the hsp3824 provides the capability to access a number of internal signals and/or data through the test port, pins test 0-7. in addition pin 1 (test_ck) is an output clock that can be used in conjunction with the data coming from the test port outputs. the test port is programmable through con?gu- ration register (cr5). there are 9 test modes assigned to the prism test port listed in the test modes table 5. table 3. adc calibration cr 1 bit 0 cr 1 bit 1 adc calibration circuit configuration 0 0 automatic real time adjustment of reference. 0 1 reference set at mid scale. 1 0 reference held at most recent value. 1 1 reference set at mid scale. table 4. rssi adc specifications parameter min typ max full scale input voltage - - 1.15 input bandwidth (0.5db) 1mhz - - input capacitance - 7pf - input impedance (dc) 1m - - table 5. test modes mode description test_clk test (7:0) 0 normal operation txclk crs, ed, 000, initial detect, reserved (1:0) 1 correlator test mode txclk mag (7:0) 2 frequency test mode dclk frq reg (7:0) 3 phase test mode dclk phase (7:0) 4 nco test mode dclk nco phase accum reg 5 sq test mode loadsq sq2 (15:8) phase variance 6 bit sync test mode 1 rxclk bit sync accum (7:0) 7 bit sync test mode 2 loadsq sq (14:7) bit sync ref- data
13 hsp3824 de?nitions normal - device in the full protocol mode (mode 3). txclk - transmit clock (pn rate). initial detect - indicates that signal quality 1 and 2 (sq1 and sq2) exceed their programmed thresholds. signal qual- ities are a function of phase error and correlator magnitude outputs. ed - energy detect indicates that the rssi value exceeds its programmed threshold. crs - indicates that a signal has been acquired (pn acquisi- tion). mag - magnitude output from the correlator. dclk - data symbol clock. frqreg - contents of the nco frequency register. phase - phase of signal after carrier loop correction. nco phaseaccumreg - contents of the nco phase accu- mulation register. loadsq - strobe that samples and updates signal quality, sq1 and sq2 values. sq2 - signal quality measure #2. signal phase variance after removal of data, 8 msbs of most recent 16-bit stored value. rxclk - receive clock (rx sample clock). nominally 22mhz. bitsyncaccum - real time monitor of the bit synchroniza- tion accumulator contents, mantissa only. sq1 - signal quality measure #1. contents of the bit sync accumulator 8 msbs of most recent 16-bit stored value. a/d_cal_ck - clock for applying a/d calibration corrections. adcal - 5-bit value that drives the d/a adjusting the a/d ref- erence. external agc control the adc cal output (pin 26) is a binary signal that ?uctuates between logic levels as the signals in the i and q channels are either at full scale or not. if the input level is too high, this output will have a higher duty cycle, and visa versa. thus, this signal could be integrated with an r-c ?lter to develop an agc control voltage. the agc feedback should be designed to drive it to 50% duty cycle. in the case that an external agc is in use then the adc calibration circuit must not be programmed for automatic level adjustment. power down modes the power consumption modes of the hsp3824 are con- trolled by the following control signals. receiver power enable (rx_pe,pin 33), which disables the receiver when inactive. transmitter power enable (tx_pe, pin 2), which disables the transmitter when inactive. reset ( reset, pin 28), which puts the receiver in a sleep mode when it is asserted at least 2 mclks after rx_pe is set at its inactive state. the power down mode where, both reset and rx_pe are used is the lowest possible power consumption mode for the receiver. exiting this mode requires a maximum of 10 m s before the device is back at its operational mode. the contents of the con?guration registers is not effected by any of the power down modes. the external processor does not have access and cannot modify any of the crs during the power down modes. no recon?guration is required when returning to operational modes. table 6 describes the power down modes available for the hsp3824 (v cc = 5.0v). the table values assume that all other inputs to the part (mclk, sclk, etc.) continue to run. 8 a/d cal test mode a/d cal_ck crs, ed, 0, adcal (4:0) 9 reserved 10 (0ah) reserved 11 reserved 12 reserved 13 reserved 14 reserved 15 reserved table 5. test modes (continued) mode description test_clk test (7:0) table 6. power down modes rx_pe tx_pe reset power (22mhz) power (44mhz) device state inactive inactive active 40mw 100mw both transmit and receive functions disabled. device in sleep mode. control interface is still active. register values are main- tained. device will return to its active state within 10 m s. inactive inactive inactive 325mw 475mw both transmit and receive operations disabled. device will become in its active state within 1 m s. inactive active inactive 335mw 500mw receiver operations disabled. receiver will return in its active state within 1 m s. active inactive inactive 335mw 500mw transmitter operations disabled. transmitter will return to its active state within 2 mclks. active active active 340mw 525mw
14 hsp3824 reset the reset signal is used during the power down mode as described in the power down mode section. the reset does not impact any of the internal con?guration registers when asserted. reset does not set the device in a default con?guration, the hsp3824 must always be programmed on power up. the hsp3824 must be programmed with reset inactive. transmitter description the hsp3824 transmitter is designed as a direct sequence spread spectrum dbpsk/dqpsk modulator. it can handle data rates of up to 4 mbps (refer to ac and dc speci?ca- tions). the major functional blocks of the transmitter include a network processor interface, dbpsk/dqpsk modulator, a data scrambler and a pn generator, as shown on figure 9. the transmitter has the capability to either generate its own synchronization preamble and header or accept the pream- ble and header information from an external source. in the ?rst case, the transmitter knows when to make the dbpsk to dqpsk switchover, as required. the preamble and header are always transmitted as dbpsk waveforms while the data packets can be con?gured to be either dbpsk or dqpsk. the preamble is used by the receiver to achieve initial pn synchronization while the header includes the necessary data ?elds of the communi- cations protocol to establish the physical layer link. there is a choice of four potential preamble/header formats that the hsp3824 can generate internally. these formats are referred to as mode 0, 1, 2 and 3. mode 0 uses the minimum number of available header ?elds while mode 3 is a full pro- tocol mode utilizing all available header ?elds. the number of the synchronization preamble bits is programmable. the transmitter accepts data from the external source, scrambles it, differentially encodes it as either dbpsk or dqpsk, and mixes it with the bpsk pn spreading. the baseband digital signals are then output to the external if modulator. the transmitter includes a programmable pn generator that can provide 11, 13, 15 or 16 chip sequences. the transmitter also contains a programmable clock divider circuit that allows for various data rates. the master clock (mclk) can be a maximum of 44mhz. the chip rates are programmed through cr3 for tx and cr2 for rx. in addition the data rate is a function of the sample clock rate (mclk) and the number of pn bits per symbol. the following equations show the symbol rate for both tx and rx as a function of mclk, chips per symbol and n. n is a programmable parameter through con?guration regis- ters cr 2and cr 3. the value of n is 2, 4, 8 or 16. n is used internally to divide the mclk to generate other required clocks for proper operation of the device. symbol rate = mclk/(n x chips per symbol). the bit rate table 7 shows examples of the relationships expressed on the symbol rate equation. the modulator is capable of switching rate automatically in the case where the preamble and header information are dbpsk modulated, and the data is dqpsk modulated. the modulator is completely independent from the demodu- lator, allowing the prism baseband processor to be used in full duplex operation. tx_i_out tx_q_out spreader tx_spread_stq 16 shift reg pn generator processor interface packet format/ tx_data dbpsk/dqpsk differential encoder shift reg tx_bit_ck scram_taps scrambler tx_chip_ck tx_scram_seed 7 7 7 7 crc-16 control port tx port i out q out figure 9. modulator diagram
15 hsp3824 header/packet description the hsp3824 is designed to handle continuous or pack- etized direct sequence spread spectrum (dsss) data transmissions. the hsp3824 can generate its own preamble and header information or it can accept them from an exter- nal source. when preamble and header are internally generated the device supports a synchronization preamble up to 256 sym- bols, and a header that can include up to ?ve ?elds. the pre- amble size and all of the ?elds are programmable. when internally generated the preamble is all 1's (before entering the scrambler). the actual transmitted pattern of the pream- ble will be randomized by the scrambler if the user chooses to utilize the data scrambling option. when the preamble is externally generated the user can choose any desirable bit pattern. note though, that if the pre- amble bits will be processed by the scrambler which will alter the original pattern unless it is disabled. the preamble is always transmitted as a dbpsk waveform with a programmable length of up to 256 symbols long. the hsp3824 requires at least 126 preamble symbols to acquire in a dual antenna con?guration (diversity), or a minimum of 78 preamble symbols to acquire under a single antenna con- ?guration. the exact number of necessary preamble sym- bols should be determined by the system designer, taking into consideration the noise and interference requirements in conjunction with the desired probability of detection vs prob- ability of false alarm for signal acquisition. the ?ve available ?elds for the header are: sfd field (16 bits) - this ?eld carries the id to establish the link. this is a mandatory ?eld for the hsp3824 to estab- lish communications. the hsp3824 will not declare a valid data packet, even if it pn acquires, unless it detects the spe- ci?c sfd. the sfd ?eld is required for both internal pream- ble/header generation and external preamble/header generation. the hsp3824 receiver can be programmed to time out searching for the sfd. the timer starts counting the moment that initial pn synchronization has been established from the preamble. signal field (8 bits) - this ?eld indicates whether the data packet that follows the header is modulated as dbpsk or dqpsk. in mode 3 the hsp3824 receiver looks at the signal ?eld to determine whether it needs to switch from dbpsk demodulation into dqpsk demodulation at the end of the always dbpsk preamble and header ?elds. service field (8 bits) - this ?eld can be utilized as required by the user. length field (16 bits) - this ?eld indicates the number of data symbols contained in the data packet. the receiver can be programmed to check the length ?eld in determining figure 10. preamble/headear modes header count cr #0 bits bit 4 bit 3 n (preamble) + 16 (header) bits 00 n (preamble) + 32 (header) bits 01 n (preamble) + 48 (header) bits 10 n (preamble) + 64 (header) bits 11 preamble (sync) n bits up to 256) preamble (sync) n bits up to 256) preamble (sync) n bits up to 256) preamble (sync) n bits up to 256) sfd 16 bits sfd 16 bits sfd 16 bits sfd 16 bits crc16 16 bits length field 16 bits signal field 8 bits service field 8 bits crc16 16 bits length field 16 bits crc16 16 bits header preamble table 7. bit rate table examples data modulation sample clock mclk (mhz) tx setup cr 3 bits 4, 3 rx set up cr 2 bits 4, 3 data rate for 11 chips/bit (mbps) data rate for 13 chips/bit (mbps) data rate for 15 chips/bit (mbps) data rate for 16 chips/bit (mbps) dqpsk 44 00 (n = 2) 00 4 3.385 2.933 2.75 dqpsk 22 01 (n = 4) 01 2 1.692 1.467 1.375 dqpsk 11 10 (n = 8) 10 1 0.846 0.733 0.688 dqpsk 5.5 11 (n = 16) 11 0. 5 0.423 0.367 0.344 dbpsk 44 00 (n = 2) 00 2 1.692 1.467 1.375 dbpsk 22 01 (n = 4) 01 1 0.846 0.733 0.688 dbpsk 11 10 (n = 8) 10 0.5 0.423 0.367 0.344 dbpsk 5.5 11 (n = 16) 11 0.25 0.212 0.183 0.171
16 hsp3824 when it needs to de-assert the md_rdy interface signal. md_rdy envelopes the received data packet as it is being output to the external processor. ccitt - crc 16 field (16 bits) - this ?eld includes the 16- bit ccitt - crc 16 calculation of the ?ve header ?elds. this value is compared with the ccitt - crc 16 code calculated at the receiver. the hsp3824 receiver can be programmed to drop the link upon a ccitt - crc 16 error or it can be programmed to ignore the error and to continue with data demodulation. the crc or cyclic redundancy check is a ccitt crc-16 fcs (frame check sequence). it is the ones compliment of the remainder generated by the modulo 2 division of the pro- tected bits by the polynominal: x 16 + x 12 + x 5 + 1 the protected bits are processed in transmit order. all crc calculations are made prior to data scrambling. a shift regis- ter with two taps is used for the calculation. it is preset to all ones and then the protected ?elds are shifted through the register. the output is then complimented and the residual shifted out msb ?rst. when the hsp3824 generates the preamble and header inter- nally it can be con?gured into one of four link protocol modes. mode 0 - in this mode the preamble is programmable up to 256 bits (all 1's) and the sfd ?eld is the only ?eld utilized for the header. this mode only supports dbpsk transmissions for the entire packet (preamble/header and data). mode 1 - in this mode the preamble is programmable up to 256 bits (all 1's) and the sfd and ccitt - crc 16 ?elds are used for the header. the data that follows the header can be either dbpsk or dqpsk. the receiver and transmitter must be pro- grammed to the proper modulation type. mode 2 - in this mode the preamble is programmable up to 256 bits (all 1's) and the sfd, length field, and ccitt - crc 16 ?elds are used for the header. the data that follows the header can be either dbpsk or dqpsk. the receiver and transmitter must be programmed to the proper modulation type. mode 3 - in this mode the preamble is programmable up to 256 bits (all 1's). the header in this mode is using all available ?elds. in mode 3 the signal ?eld de?nes the modulation type of the data packet (dbpsk or dqpsk) so the receiver does not need to be preprogrammed to anticipate one or the other. in this mode the device checks the signal ?eld for the data packet modulation and it switches to dqpsk if it is de?ned as such in the signal ?eld. note that the preamble and header are always dbpsk the modulation de?nition applies only for the data packet. this mode is called the full protocol mode in this document. figure 10 summarizes the four preamble/head or modes. in the case that the device is con?gured to accept the preamble and header from an external source it still needs to be con?gured in one of the four modes (0:3). even though the hsp3824 trans- mitter does not generate the preamble and header information the receiver needs to know the mode in use so it can proceed with the proper protocol and demodulation decisions. the following con?guration registers (cr)are used to program the preamble/header functions, more programming details about these registers can be found in the control registers section of this document: cr 0 - de?nes one of the four modes (bits 4, 3) for the tx. de?nes whether the sfd timer is active (bit 2). de?nes whether the receiver should stop demodulating after the number of sym- bols indicated in the length ?eld has been met. cr 2 - de?nes to the receiver one of the four protocol modes (bits 1, 0). indicates whether any detected ccitt - crc 16 errors need to reset the receiver (return to acquisition) or to ignore them and continue with demodulation (bit 5). speci?es a 128-bit preamble or an 80-bit preamble (bit 2). cr 3 - de?nes internal or external preamble generation (bit 2). indicates to the receiver the data packet modulation (bit 0), note that in mode 3 the contents of this register are overwritten by the information in the received signal ?eld of the header. cr 3 speci?es the data modulation type used to the transmitter (bit 1). bit 1 de?nes the contents of the signaling ?eld in the header to indicate either dbpsk or dqpsk modulation. cr 41 - de?nes the length of time that the demodulator searches for the sfd before returning to acquisition. cr 42 - the contents of this register indicate that the transmit- ted data is dbpsk. if cr 4-bit 1 is set to indicate dbpsk mod- ulation then the contents of this register are transmitted in the signal ?eld of the header. cr 43 - the contents of this register indicates that the transmit- ted data is dqpsk. if cr 4-bit 1 is set to indicate dqpsk mod- ulation then the contents of this register are transmitted in the signal ?eld of the header. cr 44, 45, 46, 47, 48 - status, read only, registers that indicate the service ?eld, data length ?eld and ccitt - crc 16 ?eld val- ues of the received header. cr 49, 50 - de?nes the transmit sfd ?eld value of the header. the receiver will always search to detect this value before it declares a valid data packet. cr 51 - de?nes the contents of the transmit service ?eld. cr 52, 53 - de?nes the value of the transmit data length ?eld. this value includes all symbols following the last header ?eld symbol. cr 54,55 - status, read only, registers indicating the calculated ccitt - crc 16 value of the most recently transmitted header. cr 56 - de?nes the number of preamble synchronization bits that need to be transmitted when the preamble is internally generated. these symbols are used by the receiver for initial pn acquisition and they are followed by the header ?elds. the full protocol requires a setting of 128d = 80h. for other applications, in general increasing the preamble length will improve low signal to noise acquisition performance at the cost of greater link overhead. for dual receive antenna operation, the minimum suggested value is 128d = 80h. for single receive antenna operation, the minimum suggested value is 80d = 50h. these suggested values include a 2 symbol tx power ampli?er ramp up. if an agc is used, its worst case settling time in sym- bols should be added to these values.
17 hsp3824 pn generator description the spread function for this radio uses short sequences. the same sequence is applied to every bit. all transmitted symbols, preamble/header and data are always spread by the pn sequence at the chip rate. the pn sequence sets the process- ing gain (pg) of the direct sequence receiver. the hsp3824 can be programmed to utilize 11,13,15 and 16 bit sequences. given the length of these programmable sequences the pg range of the hsp3824 is: from 10.41db (10 log(11)) to 12.04db (10 log(16)) the transmitter and receiver pn sequences can are pro- grammed independently. this provides additional ?exibility to the network designer. the tx sequence is set through cr 13 and cr 14 while the rx pn sequence is set through cr 20 and cr 21. a maximum of 16 bits can be programmed between the pairs of these con- ?guration registers. for tx registers cr13 and cr14 contain the high and low bytes of the sequence for the transmitter. in addition bits 5 and 6 of cr 4 de?ne the sequence length in chips per bit. cr 13, cr 14 and cr 4 must all be programmed for proper functionality of the pn generator. the sequence is transmitted msb ?rst. when fewer than 16 bits are in the sequence, the msbs are truncated. scrambler and data encoder description the data coder the implements the desired dqpsk coding as shown in the dqpsk data encoder table. this coding scheme results from differential coding of the dibits. when used in the dbpsk modes, only the 00 and 11 dibits are used. vector rota- tion is counterclockwise. the data scrambler is a self synchronizing circuit. it consist of a 7-bit shift register with feedback from speci?ed taps of the register, as programmed through cr 16. both transmitter and receiver use the same scrambling algorithm. all of the bits transmitted are scrambled, including data header and preamble. the scrambler can be disabled. scrambling provides additional spreading to each of the spectral lines of the spread ds signal. the additional spreading due to the scrambling will have the same null to null bandwidth, but it will further smear the discrete spectral lines from the pn code sequence. scrambling might be nec- essary for certain allocated frequencies to meet transmis- sion waveform requirements as de?ned by various regulatory agencies. in the absence of scrambling, the data patterns could con- tain long strings of ones or zeros. this is de?nitely the case with the a ds preamble which has a stream of up to 256 continuous ones. the continuous ones would cause the table 8. dqpsk data encoder phase shift dibits 000 +90 01 +180 11 -90 10 spectrum to be concentrated at the discrete lines de?ned by the spreading code and potentially cause interference with other narrow band users at these frequencies. additionally, the ds system itself would be moderately more susceptible to interference at these frequencies. with scrambling, the spectrum is more uniform and these negative effects are reduced, in proportion with the scrambling code length. figure 11 illustrates an example of a non scrambled trans- mission using an 11-bit code with dbpsk modulation with alternate 1's and 0's as data. the data rate is 2 mbps while the spread rate or chip rate is at 11 mcps. the 11 spectral lines resulting from the pn code can be clearly seen in fig- ure 11. in figure 12, the same signal is transmitted but with the scrambler being on. in this case the spectral lines have been smeared. figure 11. unscrambled dbpsk data of alternate 1s/0s spread with an 11-bit sequence figure 12. scrambled dbpsk data of alternate 1s/0s spread with an 11-bit sequence another reason to scramble is to gain a small measure of pri- vacy. the ds nature of the signal is easily demodulated with a correlating receiver. indeed, the data modulation can be recovered from one of the discrete spectral lines with a narrow band receiver (with a 10db loss in sensitivity). this means that the signal gets little security from the ds spreading code alone. scrambling adds a privacy feature to the waveform that would require the listener to know the scrambling parameters in order to listen in. when the data is scrambled it cannot be center 280mhz res bw 300khz vbw 100khz span 50mhz swp 20ms ref -24dbm atten 10db center 280mhz res bw 300khz vbw 100khz span 50mhz swp 20ms ref -25dbm atten 10db
18 hsp3824 defeated by listening to one of the scrambling spectral lines since the unintentional receiver in this case is too narrow band to recover the data modulation. this assumes though that each user can set up different scrambling patterns there are 9 maximal length codes that can be utilized with a generator of length 7. the different codes can be used to implement a basic privacy scheme. it needs to be clear though that this scrambling code length and the actual properties of such codes are not a major challenge for a sophisticated intentional interceptor to be listening in. this is why we refer to this scrambling advantage as a communications privacy feature as opposed to a secure communications feature. scrambling is done by a polynomial division using a pre- scribed polynomial. a shift register holds the last quotient and the output is the exclusive-or of the data and the sum of taps in the shift register. the taps and seed are program- mable. the transmit scrambler seed is programmed by cr 15 and the taps are set with cr 16. setting the seed is optional, since the scrambler is self-synchronizing and it will eventually synchronize with the incoming data after ?ashing the 7 bits stored from the previous transmission. modulator description the modulator is designed to support both dbpsk and dqpsk signals. the modulator is capable of automatically switching its rate in the case where the preamble and header are dbpsk modulated, and the data is dqpsk modulated. the modulator can support date rates up to 4 mbps. the pro- gramming details of the modulator are given at the introduc- tory paragraph of this section. the hsp3824 can support data rates of up to 4 mbps (dqpsk) with power supply voltages between 3.3v and 5.0v and data rates of up to 3 mbps with supply voltages between 2.7v and 5.5v. clear channel assessment (cca) and energy detect (ed) description the clear channel assessment (cca) circuit implements the carrier sense portion of a carrier sense multiple access (csma) networking scheme. the clear channel assess- ment (cca) monitors the environment to determine when it is feasible to transmit. the result of the cca algorithm is available in real time through output pin 32 of the device. the cca state machine in the hsp3824 can be programmed as a function of rssi, energy detected on the channel, carrier detection, and a number of on board watchdog timers to time-out under certain conditions. the cca can be also completely by-passed allowing transmissions independent of any channel conditions. the programmable cca in combi- nation with the visibility of the various internal parameters (i.e. energy detection measurement results), can assist an external processor in executing algorithms that can adapt to the environment. these algorithms can increase network throughput by minimizing collisions and reducing transmis- sions liable to errors. there are two measures that are used in the cca assess- ment. the receive signal strength (rssi) which measures the energy at the antenna and the carrier sense (cs), which is triggered upon valid pn correlation of the baseband pro- cessor (hsp3824). both indicators are used since interfer- ence can trigger the signal strength indication, but it will not trigger the carrier sense. the carrier sense, however, is slower to respond than the signal strength and it becomes active only when a spread signal with identical pn code has been detected, so it is not adequate in itself. note that the cs is also vulnerable to false alarms. the cca looks for changes in these measurements and decides its state based on these measures and the time that has elapsed since the figure 13. cca functional flow diagram ed < thresh clear cs > thresh ed < thresh cs > thresh ed > thresh ed >thresh cnt = cnt + 1 ed >thresh cs < thresh reset cnt busy busy cnt < n cnt = n reset cnt clear watchdog timer reset on cca = clear reset on m ms timeout reset continuous cca to mac ed cs cca latch holds last decision busy cs< thresh ed < thresh wait for change in ed or cs status or timer timeout
19 hsp3824 channel was last clear. if a source of interference makes it look like the channel is occupied, the circuit will detect a sig- nal without carrier and will wait a proscribed time before deciding to transmit over the interference. the receive signal strength indication (rssi) measurement is an analog input to the hsp3824 from the successive if stage of the radio. the rssi adc converts it within the baseband processor and it compares it to a programmable threshold. this threshold is normally set to between -70 and -80dbm. this measure is used in the acquisition decision and is also passed to the clear channel assessment logic. the state diagram in figure 13 shows the operation of the clear channel assessment state machine. the energy detection (ed) signal is the digitized rssi signal. the carrier sense (cs) input is derived from a combination of the signal quality 2 (sq2) based on phase error and the sig- nal quality 1(sq1) based on pn correlator magnitude out- puts. both signal quality measures and the ed input are differentiated to sense when they change. these change detectors and the watchdog timer time out output are com- bined to initiate a clear channel assessment decision. the cca algorithm will always declare the channel busy if cs is active. if only ed is active the state machine will ini- tially declare a busy channel and at the same time it will start timing ed until it meets the programmed time out count. when the time out expires the state machine will declare the channel as being clear even if the ed is still active. this will prevent the transmitter locking out permanently on some persisting interference. this time out period is programmable by 2 parameters that de?ne an inner count m and an outer count n. the total time out period is determined by the time corresponding to the product of mxn. the value of the inner counter m is programmable through cr 17 while the value of the outer counter n is programmable through cr 18. the state machine cycles m times the n count before it asserts cca, declaring the channel as clear for transmission. note that the counters are automatically reset to restart the count when cs is detected to be active. in summary the cca state machine has four basic states. the ?rst state clears the cca when both the cs and ed are inactive. this indicates that the channel is truly clear. the second state sets the cca to busy when the cs is active and the ed is inactive. this corresponds to a channel where the signal just went away or dropped below threshold but the carrier is still being sensed. the third state sets the cca to busy and resets the cycle counter when the ed and cs are both active. this is an obviously busy channel. the fourth state increments the cycle counter if the cs is inactive and the ed is active, and sets the cca to busy if the count is less than n. this is where the channel has just had a new signal come up and the carrier has not yet been acquired or where an interferer turns on. if the cycle counter reaches n, the counter is reset and the cca is set to clear. this happens on interference that per- sists. if the channel has interference, it may be low enough to allow communications. the cca state machine does not in?uence any of the receive or transmit operations within the hsp3824. the cca algorithm output is an indication to the network processor. the processor can ignore this indicator and decide to have the hsp3824 transmit regardless of the state of cca. the con?guration registers effecting the cca algorithm operation are summarized below (more programming details on these registers can be found under the control registers section of this document). the cca output from pin 32 of the device can be de?ned as active high or active low through cr 9 (bit 5). the rssi threshold is set through cr19. if the actual rssi value from the adc exceeds this threshold then ed becomes active. the instantaneous rssi value can be monitored by the exter- nal network processor by reading cr 10. the programmable thresholds on the two signal quality measurements are set through cr22, 23, 30, and 31. signal quality 1 and 2 thresh- olds derive the state of the carrier sense. more details on sq are included under the receiver section of this document. figure 14. demodulator block diagram signal quality 1 correlator 16tap magnitude and phase distribution a/d section a/d section correlator 16tap data descram dif dec psk demod phase rotate timing avg phase freq. avg phase error abs phase error signal quality 2 symbol timing i q symbol timing nco lead /lag filter control rxd
20 hsp3824 finally, cr 17 and cr 18 are used to set the time out parameters before the cca algorithm declares permission for transmission. receiver description the receiver portion of the baseband processor, performs adc conversion and demodulation of the spread spectrum signal. it correlates the pn spread symbols, then demodu- lates the dbpsk or dqpsk symbols. the demodulator includes a frequency loop that tracks and removes the car- rier frequency offset. in addition it tracks the symbol timing, and differentially decodes and descrambles the data. the data is output through the rx port to the external processor. a common practice for burst mode communications systems is to differentially modulate the signal, so that a dpsk demodulator can be used for data recovery. this form of demodulator uses each symbol as a phase reference for the next one. it offers rapid acquisition and tolerance to rapid phase ?uctuations at the expense of lower bit error rate (ber) performance. the prism baseband processor, hsp3824 uses differential demodulation for the initial acquisition portion of the pro- cessing and then switches to coherent demodulation for the rest of the acquisition and data demodulation. the hsp3824 is designed to achieve rapid settling of the carrier tracking loop during acquisition. coherent processing substantially improves the ber performance margin. rapid phase ?uctu- ations are handled with a relatively wide loop bandwidth. the baseband processor uses time invariant correlation to strip the pn spreading and polar processing to demodulate the resulting signals. these operations are illustrated in fig- ure 14 which is an overall block diagram of the receiver pro- cessor. input samples from the i and q adc converters are correlated to remove the spreading sequence. the magni- tude of the correlation pulse is used to determine the symbol timing. the sample stream is decimated to the symbol rate and the phase is corrected for frequency offset prior to psk demodulation. phase errors from the demodulator are fed to the nco through a lead/lag ?lter to achieve phase lock. the variance of the phase errors is used to determine signal quality for acquisition and lock detection. acquisition description the prism baseband processor uses either a dual antenna mode of operation for compensation against multipath inter- ference losses or a single antenna mode of operation with faster acquisition times. two antenna acquisition during the 2 antenna (diversity) mode the two antennas are scanned in order to ?nd the one with the best representation of the signal. this scanning is stopped once a suitable signal is found and the best antenna is selected. a projected worst case time line for the acquisition of a signal in the two antenna case is shown in figure 15. the synchroni- zation part of the preamble is 128 symbols long followed by a 16-bit sfd. the receiver must scan the two antennas to deter- mine if a signal is present on either one and, if so, which has the better signal. the timeline is broken into 16 symbol blocks (dwells) for the scanning process. this length of time is neces- sary to allow enough integration of the signal to make a good notes: 1. worst case timing; antenna dwell starts before signal is full strength. 2. time line shown assumes that antenna 2 gets insufficient signal. figure 15. dual antenna acquisition timeline figure 16. single antenna acquisition timeline 16 symbols 126 symbol sync sfd just missed det ant1 symb timing detect ant1 check ant2 tx power ramp no sig found ant2 16 symbols 16 symbols 16 symbols 16 symbols 16 symbols 16 symbols 7s 16 symbols a1 a2 a1 a2 a1 a2 a1 a1 a1 detect ant1 sfd det start data seed descrambler 7s a1 check ant2 internal set up time verify ant1 2 2 16 symbols 78 symbol sync sfd just missed det detect tx power ramp 16 symbols 16 symbols 16 symbols 7 sym 16 symbols symb timing verify sfd det start data seed descrambler 7 sym internal set up time
21 hsp3824 acquisition decision. this worst case time line example assumes that the signal is present on antenna a1 only (a2 is blocked). it further assumes that the signal arrives part way into the ?rst a1 dwell such as to just barely miss detection. the signal and the scanning process are asynchronous and the signal could start anywhere. in this timeline, it is assumed that all 16 symbols are present, but they were missed due to power ampli?er ramp up. since a2 has insuf?cient signal, the ?rst a2 dwell after the start of the preamble also fails detec- tion. the second a1 dwell after signal start is successful and a symbol timing measurement is achieved. meanwhile signal quality and signal frequency measure- ments are made simultaneous with symbol timing measure- ments. when the bit sync level, sq1, and phase variance sq2 are above their user programmable thresholds, the sig- nal is declared present for the antenna with the best signal. more details on the signal quality estimates and their pro- grammability are given in the acquisition signal quality parameters section of this document. at the end of each dwell, a decision is made based on the rel- ative values of the signal qualities of the signals on the two antennas. in the example, antenna a1 is the one selected, so the recorded symbol timing and carrier frequency for a1 are used thereafter for the symbol timing and the pll of the nco to begin carrier de-rotation and demodulation. prior to initial acquisition the nco was inactive and dpsk demodulation processing was used. carrier phase measure- ment are done on a symbol by symbol basis afterward and coherent dpsk demodulation is in effect. after a brief setup time as illustrated on the timeline of figure 15, the signal begins to emerge from the demodulator. if the descrambler is used it takes 7 more symbols to seed the descrambler before valid data is available. this occurs in time for the sfd to be received. at this time the demodulator is tracking and in the coherent psk demodulation mode it will no longer scan antennas. one antenna acquisition when only one antenna is being used, the user can delete the antenna switch and shorten the acquisition sequence. figure 16 shows the single antenna acquisition timeline. it uses a 78 symbol sequence with 2 more for power ramping of the rf front of the radio. this scheme deletes the second antenna dwells but performs the same otherwise. it veri?es the signal after initial detection for lower false alarm proba- bility. acquisition signal quality parameters two measures of signal quality are used to determine acqui- sition and drop lock decisions. the ?rst method of determin- ing signal presence is to measure the correlator output (or bit sync) amplitude. this measure, however, ?attens out in the range of high ber and is sensitive to signal amplitude. the second measure is phase noise and in most ber sce- narios it is a better indication of good signals plus it is insen- sitive to signal amplitude. the bit sync amplitude and phase noise are integrated over each block of 16 symbols used in acquisition or over blocks of 128 symbols in the data demod- ulation mode. the bit sync amplitude measurement repre- sents the peak of the correlation out of the pn correlator. figure 17 shows the correlation process. the signal is sam- pled at twice the chip rate (i.e. 22 msps). the one sample that falls closest to the peak is used for a bit sync amplitude sample for each symbol. this sample is called the on-time sample. high bit sync amplitude means a good signal. the early and late samples are the two adjacent samples and are used for tracking. the other signal quality measurement is based on phase noise and that is taken by sampling the correlator output at the correlator peaks. the phase changes due to scrambling are removed by differential demodulation during initial acquisition. then the phase, the phase rate and the phase variance are measured and integrated for 16 symbols. the phase variance is used for the phase noise signal quality measure. low phase noise means a stronger received signal. procedure to set acq. signal quality parameters (example) there are four registers that set the acquisition signal quality thresholds, they are: cr 22, 23, 30, and 31 (rx_sqx_in_acq). each threshold consists of two bytes, high and low that hold a 16-bit number. figure 17. correlation process t0 + 1 m s correlator correlation peak t0 + 2 m s t0 correlator output is the result of correlating the pn sequence with the received signal samples at 2x chip rate early on-time late output repeats correlation time
22 hsp3824 these two thresholds, bit sync amplitude cr (22 and 23) and phase error cr (30 and 31) are used to determine if the desired signal is present. if the thresholds are set too low, there is the probability of missing a high signal to noise detection due to processing a false alarm. if they are set too high, there is the probability of missing a low signal to noise detection. for the bit sync amplitude, high actually means high amplitude while for phase noise high means high snr or low noise. a recommended procedure is to set these thresholds individu- ally optimizing each one of them to the same false alarm rate with no desired signal present. only the background environ- ment should be present, usually additive gaussian white noise (agwn). when programming each threshold, the other threshold is set so that it always indicates that the signal is present. set register cr22 to 00h while trying to determine the value of the phase error signal quality threshold for regis- ters cr 30 and 31. set register cr30 to ffh while trying to determine the value of the bit sync. amplitude signal quality threshold for registers 22 and 23. monitor the carrier sense (crs) output (test 7, pin 46) and adjust the threshold to pro- duce the desired rate of false detections. crs indicates valid initial pn acquisition. after both thresholds are programmed in the device the crs rate is a logic and of both signal qualities rate of occurrence over their respective thresholds and will therefore be much lower than either. pn correlator description the pn correlator is designed to handle bpsk spreading with carrier offsets up to 50ppm and 11,13,15 or 16 chips per symbol. since the spreading is bpsk, the correlator is implemented with two real correlators, one for the i and one for the q channel.the same sequence is always used for both i an q correlators. the tx sequence can be pro- grammed as a different sequence from the rx sequence. this allows a full duplex link with different spreading parame- ters for each direction. the correlators are time invariant matched ?lters otherwise known as parallel correlators. they use two samples per chip. the correlator despreads the samples from the chip rate back to the original data rate giving 10.4db processing gain for 11 chips per bit. while despreading the desired sig- nal, the correlator spreads the energy of any non correlating interfering signal. based on the fact that correlator output pulse is used for bit timing, the hsp3824 can not be used for any non spread applications. in programming the correlator functions, there are two sets of con?guration registers that are used to program the spread sequences of the transmitter and the receiver. they are cr 13 and 14 for transmitter and cr 20 and 21 for the receiver. in addition, cr2 and cr3 de?ne the sequence length or chips per symbol for the receiver and transmitter respectively. these are carried in bits 6 and 7 of cr2 and bits 5 and 6 of cr3. more programming details are given in the control registers section of this document. data demodulation and tracking description the signal is demodulated from the correlation peaks tracked by the symbol timing loop (bit sync). the frequency and phase of the signal is corrected from the nco that is driven by the phase locked loop. demodulation of the dpsk data in the early stages of acquisition is done by delay and subtraction of the phase samples. once phase locked loop tracking of the carrier is established, coherent demodulation is enabled for better performance. averaging the phase errors over 16 symbols gives the necessary frequency infor- mation for proper nco operation. the signal quality is taken as the variance in this estimate. there are two signal quality measurements that are per- formed in real time by the device and they set the demodula- tor performance. the thresholds for these signal quality measurements are user programmable. the same two sig- nal quality measures, phase error and bit sync. amplitude, that are used in acquisition are also used for the data drop lock decision. the data thresholds, though, are programmed independently from the acquisition thresholds. if the radio uses the network processor to determine when to drop the signal, the thresholds for these decisions should be set to their limits allowing data demodulation even with poor signal reception. under this con?guration the hsp3824 data moni- tor mechanism is essentially bypassed and data monitoring becomes the responsibility of the network processor. these signal quality measurements are integrated over 128 symbols as opposed to 16 symbol intervals for acquisition, so the minimum time to drop lock based with these thresholds is 128 symbols or 128ms at 1 msps. note that other than the data thresholds, non-detection of the sfd can cause the hsp3824 to drop lock and return its acquisition mode. con?guration register 41 sets the search timer for the sfd. this register sets this time-out length in symbols for the receiver. if the time out is reached, and no sfd is found, the receiver resets to the acquisition mode. the suggested value is preamble symbols + 16 symbols. if several transmit pream- ble lengths are used by various transmitters in a network, the longest value should be used for the receiver settings. procedure to set signal quality registers cr 26, 27, 34, and 35 (rx_sqx_in_data) are pro- grammed to hold the threshold values that are used to drop lock if the signal quality drops below their values. these can be set to their limit values if the external network processor is used for drop lock decisions instead of the hsp3824 demodulator. the signal quality values are averaged over 128 symbols and if the bit sync amplitude value drops below its threshold or the phase noise rises over its threshold, the link is dropped and the receiver returnes to the acquisition mode. these values should typically be different for bpsk and qpsk since the operating point in snr differs by 3db. if the receiver is intended to receive both bpsk and qpsk modulations, a compromise value must be used or the net- work processor can control them as appropriate.
23 hsp3824 the suggested method of optimization is to set the transmit- ter in a continuous transmit mode. then, measure the time until the receiver drops lock at low signal to noise ratio. each of the 2 thresholds should be set individually to the same drop lock time. while setting thresholds for one of the signal qualities the other should be con?gured at its limit so it does not in?uence the drop lock decisions. set cr 26 to 00h while determining the value of cr 34 and 35 for phase error threshold. set cr 34 to ffh while determining the value of cr 26 and 27 for bit sync. amplitude threshold. assuming a 10e-6 ber operating point, it is suggested that the drop lock thresholds are set at 10e-3 ber, with each threshold adjusted individually. note that the bit sync amplitude is linearly proportional to the signal amplitude at the adc converters. if an agc system is being used instead of a limiter, the bit sync amplitude thresh- old should be set at or below the minimum amplitude that the radio will see at its sensitivity level. data decoder and descrambler description the data decoder that implements the desired dqpsk cod- ing/decoding as shown in dqpsk data decoder table 9. this coding scheme results from differential coding of the dibits. when used in the dbpsk modes, only the 00 and 11 dibits are used. vector rotation is counterclockwise. the data scrambler and de-scrambler are self synchronizing circuits. they consist of a 7-bit shift register with feedback of some of the taps of the register. the scrambler can be dis- abled for measuring rf carrier suppression. the scrambler is designed to insure smearing of the discrete spectrum lines produced by the pn code. one thing to keep in mind is that both the differential decod- ing and the descrambling when used cause error extension. this causes the errors to occur in groups of 4 and 6. this is due to two properties of the processing. first, the differential decoding process causes errors to occur in pairs. when a symbol error is made, it is usually a single bit error even in qpsk mode. when a symbol is in error, the next symbol will also be decoded wrong since the data is encoded in the change from one symbol to the next. thus, two errors are made on two successive symbols. in qpsk mode, these may be next to one another or separated by up to 2 bits. table 9. dqpsk data decoder phase shift dibits 000 +90 01 +180 11 -90 10 secondly, when the bits are processed by the descrambler, these errors are further extended. the descrambler is a 7-bit shift register with one or more taps exclusive ored with the bit stream. if for example the scrambler polynomial uses 2 taps that are summed with the data, then each error is extended by a factor of three. since the dpsk errors are close together, however, some of them can be canceled in the descrambler. in this case, two wrongs do make a right, so the observed errors can be in groups of 4 instead of 6. descrambling is done by a polynomial division using a pre- scribed polynomial. a shift register holds the last quotient and the output is the exclusive-or of the data and the sum of taps in the shift register. the taps and seed are programmable. the transmit scrambler seed is programmed by cr 15 and the taps are set with cr 16. one reason for setting the seed is that it can be used to make the sfd scrambling the same every packet so that it can be recognized in its scrambled state. demodulator performance this section indicates the theoretical performance and typi- cal performance measures for a radio design. the perfor- mance data below should be used as a guide. the actual performance depends on the application, interference envi- ronment, rf/if implementation and radio component selec- tion in general. overall eb/n0 versus ber performance the prism chip set has been designed to be robust and energy ef?cient in packet mode communications. the demodulator uses coherent processing for data demodula- tion. figure 18 below shows the performance of the base- band processor when used in conjunction with the hsp3724 if limiter and the prism recommended if ?lters. off the shelf test equipment are used for the rf processing. the curves should be used as a guide to assess performance in a complete implementation. factors for carrier phase noise, multipath, and other degra- dations will need to be considered on an implementation by implementation basis in order to predict the overall perfor- mance of each individual system. figure 18 shows the curve for theoretical dbpsk/dqpsk demodulation with coherent demodulation as well as the prism performance measured for dbpsk and dqpsk. the losses include rf and if radio losses; they do not re?ect the hsp3824 losses alone. these are more realistic measure- ments. the hsp3824 baseband losses from theoretical by themselves are a small percentage of the overall loss. the prism demodulator performs at less than 3db from the- oretical in a awgn environment with low phase noise local oscillators. the observed errors occurred in groups of 4 and 6 errors and rarely singly. this is because of the error extension properties of differential decoding and descrambling.
24 hsp3824 figure 18. ber vs eb/n0 performance clock offset tracking performance the prism baseband processor is designed to accept data clock offsets of up to 25ppm for each end of the link (tx and rx). this effects both the acquisition and the tracking performance of the demodulator. the budget for clock offset error is 0.75db at 50ppm as shown in figure 19. figure 19. ber vs clock offset carrier offset frequency performance the correlators in the baseband processor are time invariant matched ?lter correlators otherwise known as parallel corre- lators. they use two samples per chip and are tapped at every other shift register stage. their performance with car- rier frequency offsets is determined by the phase roll rate due to the offset. for an offset of +50ppm (combined for both tx and rx) will cause the carrier to phase roll 22.5 degrees over the length of the correlator. this causes a loss of 0.22db in correlation magnitude which translates directly to eb/n0 performance loss. in the prism chip design, the corr- elator is not included in the carrier phase locked loop correc- tion, so this loss occurs for both acquisition and data. figure 20 shows the loss versus carrier offset taken out to +350khz (120khz is 50ppm at 2.4ghz). 1e-09 1e-08 1e-07 1e-06 1e-05 1e-04 1e-03 1e-02 1e-01 15.4 14.4 13.4 12.4 11.4 10.4 9.4 8.4 eb/n0 in db ber theory (dbpsk) dqpsk dbpsk 1e-5 1e-4 1e-3 -100 -60 -20 20 60 100 offset in ppm ber figure 20. ber vs carrier offset i/q amplitude imbalance imbalances in the signal cause differing effects depending on where they occur. in a system using a limiter, if the imbal- ances are in the transmitter, that is, before the limiter, ampli- tude imbalances translate into phase imbalances between the i and q symbols. if they occur in the receiver after the limiter, they are not converted to phase imbalances in the symbols, but into vector phase imbalances on the composite signal plus noise. the following curve shows data taken with amplitude imbalances in the transmitter. starting at the bal- anced condition, i = 100% of q, the bit error rate degrades by two orders of magnitude for a 3db drop in i (70%). figure 21. i/q imbalance effects a default register con?guration the registers in the hsp3824 are addressed with 14-bit num- bers where the lower 2 bits of a 16-bit hexadecimal address are left as unused. this results in the addresses being in increments of 4 as shown in the table below. table 10 shows the register values for a default full protocol con?guration (mode 3) with a single antenna. the data is transmitted as dqpsk. this is a recommended con?guration for initial test and veri?cation of the device and /or the radio design. the user can later modify the cr contents to re?ect the system and the required performance of each speci?c application. 1e-6 1e-5 1e-4 1e-3 -350 -250 -150 -50 50 150 250 350 frequency offset (khz) ber 1e-05 1e-04 1e-03 1e-02 1e-01 100 92 88 80 76 72 percent amplitude balance bit error rate 96 84 68
25 hsp3824 table 10. control register values for single antenna acquisition register name type reg addr in hex qpsk bpsk cr0 modem config. reg a r/w 00 3c 64 cr1 modem config. reg b r/w 04 00 00 cr2 modem config. reg c r/w 08 07 24 cr3 modem config. reg d r/w 0c 04 07 cr4 internal test register a r/w 10 00 00 cr5 internal test register b r/w 14 00 00 cr6 internal test register c r 18 x x cr7 modem status register a r 1c x x cr8 modem status register b r 20 x x cr9 i/o definition register r/w 24 00 00 cr10 rssi valuestatus register r 28 x x cr11 adc_cal_pos register r/w 2c 01 01 cr12 adc_cal_neg register r/w 30 fd fd cr13 tx_spread sequence(high) r/w 34 05 05 cr14 tx_spread sequence (low) r/w 38 b8 b8 cr15 scramble_seed r/w 3c 7f 7f cr16 scramble_tap (rx and tx) r/w 40 48 48 cr17 cca_timer_th r/w 44 2c 2c cr18 cca_cycle_th r/w 48 03 03 cr19 rssi_th r/w 4c 1e 1e cr20 rx_spread sequence (high) r/w 50 05 05 cr21 rx_sread sequence (low) r/w 54 b8 b8 cr22 rx_sq1_ in_acq (high) threshold r/w 58 01 01 cr23 rx-sq1_ in_acq (low) threshold r/w 5c e8 e8 cr24 rx-sq1_ out_acq (high) read r 60 x x cr25 rx-sq1_ out_acq (low) read r 64 x x cr26 rx-sq1_ in_data (high) threshold r/w 68 0f 0f cr27 rx-sq1-sq1_ in_data (low) threshold r/w 6c ff ff cr28 rx-sq1_ out_data (high)read r 70 x x cr29 rx-sq1_ out_data (low) read r 74 x x cr30 rx-sq2_ in_acq (high) threshold r/w 78 00 00
26 hsp3824 cr31 rx-sq2- in-acq (low) threshold r/w 7c ca ca cr32 rx-sq2_ out_acq (high) read r 80 x x cr33 rx-sq2_ out_acq (low) read r 84 x x cr34 rx-sq2_in_data (high)threshold r/w 88 09 09 cr35 rx-sq2_ in_data (low) threshold r/w 8c 80 80 cr36 rx-sq2_ out_data (high) read r 90 x x cr37 rx-sq2_ out_data (low) read r 94 x x cr38 rx_sq_read; full protocol r 98 x x cr39 reserved w 9c 00 00 cr40 reserved w a0 00 00 cr41 uw_time out_length r/w a4 90 90 cr42 sig_dbpsk field r/w a8 0a 0a cr43 sig_dqpsk field r/w ac 14 14 cr44 rx_ser_field r b0 x x cr45 rx_len field (high) r b4 x x cr46 rx_len field (low) r b8 x x cr47 rx_crc16 (high) r bc x x cr48 rx_crc16 (low) r c0 x x cr49 uw -(high) r/w c4 f3 f3 cr50 uw _(low) r/w c8 a0 a0 cr51 tx_ser_f r/w cc 00 00 cr52 tx_len (high) r/w d0 ff ff cr53 tx_len(low) r/w d4 ff ff cr54 tx_crc16 (high) r d8 x x cr55 tx_crc16 (low) r dc x x cr56 tx_prem_len r/w e0 80 80 table 10. control register values for single antenna acquisition (continued) register name type reg addr in hex qpsk bpsk
27 hsp3824 control registers the following tables describe the function of each control register along with the associated bits in each control register. configuration register 0 address (0h) modem configuration register a bit 7 this bit selects the transmit antenna, controlling the output ant_sel pin. it is only used in half duplex mode. (bit 5 = 0) logic 1 = antenna a. logic 0 = antenna b. bit 6 in single antenna operation this bit is used as the output of the ant_sel pin. in dual antenna mode this bit is ignored. logic 1 = antenna a. logic 0 = antenna b. bit 5 this control bit is used to select between full duplex and half duplex operation. if set for full duplex operation, the ant_sel pin reflects the setting of cr0 bit 7 when tx_pe is active and reflects the receivers choice when tx_pe is inactive. in full duplex operation, the ant_sel pin always reflects the receivers choice antenna. logic 1 = full duplex. logic 0 = half duplex. bit 4, 3 these control bits are used to select one of the four input preamble header modes for transmitting data. the preamble and header are dbpsk for all modes of operation. mode 0 is followed by dbpsk data. for modes 1-3, the data can be configured as either dbpsk or dqpsk. this is a dont care if the header is generated externally. bit 2 this control bit is used to enable the sfd (start frame delimiter) timer. if the time is set and expires before the sfd has been detected, the hsp3824 will return to its acquisition mode. logic 1: enables the sfd timer to start counting once the pn acquisition has been achieved. logic 0: disables the sfd timer. bit 1 this control bit enables counting the number of data bits per the length field embedded in the header. only used in header modes 2 and 3. then according to the count it returns the processor into its acquisition mode at the end of the count. if length field is 0000h, modem will reset at end of sfd regardless of this bit setting. logic 1 = enable length time out. logic 0 = disabled. bit 0 unused dont care. configuration register 1 address (04h) modem configuration register b bit 7 when active this bit maintains the rxclk and txlk rates constant for preamble and data transfers even if the data is modulated in dqpsk. this bit is used if the external processor can not accommodate rate changes. this is an active high signal. the rate used is the qpsk rate and the bpsk header bits are double clocked. bit 6, 5, 4, 3, 2 these control bits are used to define a binary count (n) from 0 - 31. this count is used to assert tx_rdy n - clocks (txclk) before the beginning of the first data bit. if this is set to zero, then the tx_rdy will be asserted immediately after the last bit of the preamble header. bit 1 when active the internal a/d calibration circuit sets the reference to mid-scale. when inactive then the calibration cir- cuit adjusts the reference voltage in real time to optimize i, q levels. logic 1 = reference set at mid-scale (fixed). logic 0 = real time reference adjustment. bit 0 when active the a/d calibration circuit is held at its last value. logic 1 = reference held at the most recent value. logic 0 = real time reference level adjustment. mode bit 4 bit 3 mode description 0 0 0 preamble with sfd field. 1 0 1 preamble with sfd, and crc16. 2 1 0 preamble with sfd, length, and crc16. 3 1 1 full preamble and header.
28 hsp3824 configuration register 2 address (08h) modem configuration register c bit 7, 6 these control bits are used to select the number of chips per symbol used in the i and q paths of the receiver matched filter correlators (see table below). bit 5 this control bit is used to disable the crc16 check. when this bit is set, the processor will accept the received packet and any packet error checks have to be detected externally. the hsp3824 will remain in the receive mode until either the carrier is lost or the network processor resets the device to the acquisition mode, or if, in modes 2 or 3, the length times out. logic 1 = disable receiver error checks. logic 0 = enable receiver checks. bit 4, 3 these control bits are used to select the divide ratio for the demodulators receive chip clock timing.the value of n is determined by the following equation: symbol rate = mclk/(n x chips per symbol). bit 2 this control bit sets the receiver into single or dual antenna mode. the preamble acquisition processing length and whether the modem scans antennas is controlled by this bit. if in single antenna mode, the ant_sel pin reflects cr0 bit 6 otherwise it reflects the receivers choice of antenna. logic 0 = acquisition processing is for dual antenna acquisition. logic 1 = acquisition processing is for single antenna acquisition. bit 1, 0 these control bits are used to indicate one of the four preamble header modes for receiving data. each of the modes includes different combinations of header fields. users can choose the mode with the fields that are more appropriate for their networking requirements. the header fields that are combined to form the various modes are: ? sfd ?eld ? crc16 ?eld ? data length ?eld (indicates the number of data bits that follow the header information) ? full protocol header configuration register 3 address (0ch) modem configuration register d bit 7 reserved (must set to 0). chips per symbol bit 7 bit 6 11 0 0 13 0 1 15 1 0 16 1 1 master clock/n bit 4 bit 3 n = 2 0 0 n = 4 0 1 n = 8 1 0 n = 16 1 1 input mode bit 1 bit 0 receive preamble - header fields 0 0 0 preamble, with sfd field 1 0 1 preamble, with sfd, crc16 2 1 0 preamble, with sfd length, crc16 3 1 1 preamble, with full protocol header
29 hsp3824 bit 6, 5 these control bits combined are used to select the number of chips per symbol used in the i and q transmit paths (see table below). bit 4, 3 these control bits are used to select the divide ratio for the transmit chip clock timing. note: the value of n is determined by the following equation: symbol rate = mclk/(n x chips per symbol) bit 2 this control bit is used to select the origination of preamble/header information. logic 1: the hsp3824 generates the preamble and header internally by formatting the programmed header information and generating a tx_rdy to indicate the beginning of the data packet. logic 0: accepts the preamble/header information from an externally generated source. bit 1 this control bit is used to indicate the signal modulation type for the transmitted data packet. when configured for mode 0 header, or mode 3 and external header, this bit is ignored. see register 0 bits 4 and 3. logic 1 = dbpsk modulation for data packet. logic 0 = dqpsk modulation for data packet. bit 0 this control bit is used to indicate the signal modulation type for the received data packet used only with header modes 1 and 2. see register 2 bits 1 and 0. logic 1 = dbpsk. logic 0 = dqpsk. configuration register 4 address (10h) internal test register a bit 7 - 0 these control bits are used to direct various internal signals to test port output pins. these internal signals are moni- tored to fault isolate the device at manufacturing testing. during normal operation, the value 0h is recommended. this will result to the following signals becoming available at the output test pins of the device: pin 46 (test7): carrier sense (crs), a logic 1 indicates pn lock. pin 45 (test6): energy detect (ed), a logic 1 indicates that there is energy detected in the channel. the ed goes active when the rssi exceeds the threshold level programmed by the user. pin 1 (test_ck): pn clock. configuration register 5 address (14h,18h) internal test register b bits 7 - 0 these bits need to be programmed to 0h. they are used for manufacturing test only. configuration register 7 address (1ch) modem status register a bit 7 this bit indicates the status of the tx_rdy output pin. tx_rdy is used only when the hsp3824 generates the pre- amble/header data internally. logic 1: indicates that the hsp3824 has completed transmitting preamble header information and is ready to accept data from the external source (i.e. mac) to transmit. logic 0: indicates that the hsp3824 is in the process of transmitting preamble header information. bit 6 this status bit indicates the antenna selected by the device. logic 0: antenna a is selected. logic 1: antenna b is selected. configuration register 3 address (0ch) modem configuration register d (continued) chips per bit 6 bit 5 11 0 0 13 0 1 15 1 0 16 1 1 master bit 4 bit 3 n = 2 0 0 n = 4 0 1 n = 8 1 0 n = 16 1 1
30 hsp3824 bit 5 this status bit indicates the present state of clear channel assessment (cca) which is output pin 32. the cca is being asserted as a result of a channel energy monitoring algorithm that is a function of rssi, carrier sense, and time out counters that monitor the channel activity. bit 4 this status bit, when active indicates carrier sense, or pn lock. logic 1: carrier present. logic 0: no carrier sense. bit 3 this status bit indicates whether the rssi signal is above or below the programmed rssi 6-bit threshold setting. this signal is referred as energy detect (ed). logic 1: rssi is above the programmed threshold setting. logic 0: rssi is below the programmed threshold setting. bit 2 this bit indicates the status of the output control pin md_rdy (pin 34). it signals that a valid preamble/header has been received and that the next available bit on the txd bus will be the first data packet bit. logic 1: envelopes the data packet as it becomes available on pin 3 (txd). logic 0: no data packet on txd serial bus. bit 1 this status bit indicates whether the external device has acknowledged that the channel is clear for transmission. this is the same as the input signal tx_pe on pin 2. logic 1 = acknowledgment that channel is clear to transmit. logic 0 = channel is not clear to transmit. bit 0 this status bit indicates that a valid crc16 has been calculated. the crc16 is calculated on the header information. the crc16 does not cover the preamble bits. logic 1 = valid crc16 check. logic 0 = invalid crc16 check. configuration register 8 address (20h) modem status register b bit 7 this status bit is meaningful only when the device operates under the full protocol mode. errors imply crc errors of the header fields. logic 0 = valid packet received. logic 1 = errors in received packet. bit 6 this bit is used to indicate the status of the sfd search timer. the device monitors the incoming header for the sfd. if the timer, times out the hsp3824 returns to its signal acquisition mode looking to detect the next preamble and header. logic 1 = sfd not found, return to signal acquisition mode. logic 0 = no time out during sfd search. bit 5 this status bit is used to indicate the modulation type for the data packet. this signal is generated by the header de- tection circuitry in the receive interface. logic 0 = dbpsk. logic 1 = dqpsk. bit 4 unused, dont care. bit 3 unused, dont care. bit 2 unused, dont care. bit 1 unused, dont care. bit 0 unused, dont care. configuration register 9 address (24h) i/o definition register this register is used to define the phase of clocks and other interface signals. bit 7 this bit needs to always be set to logic 0. bit 6 this control bit selects the active level of the md_rdy output pin 34. logic 1 = md_rdy is active 0. logic 0 = md_rdy is active 1. configuration register 7 address (1ch) modem status register a (continued)
31 hsp3824 bit 5 this control bit selects the active level of the clear channel assessment (cca) output pin 32. logic 1 = cca active 1. logic 0 = cca active 0. bit 4 this control bit selects the active level of the energy detect (ed) output which is an output pin at the test port, pin 45. logic 1 = ed active 0. logic 0 = ed active 1. bit 3 this control bit selects the active level of the carrier sense (crs) output pin which is an output pin at the test port, pin 46. logic 1 = crs active 0. logic 0 = crs active 1. bit 2 this control bit selects the active level of the transmit ready (tx_rdy) output pin 5. logic 1 = tx_rdy active 0. logic 0 = tx_rdy active 1. bit 1 this control bit selects the active level of the transmit enable (tx_pe) input pin 2. logic 1 = tx_pe active 0. logic 0 = tx_pe active 1. bit 0 this control bit selects the phase of the transmit output clock (txclk) pin 4. logic 1 = inverted txclk. logic 0 = non-inverted txclk configuration register 10 address (28h) rssi value register bits 0 - 7 this is a read only register reporting the value of the rssi analog input signal from the on chip 6-bit adc. this register is updated at (chip rate/11). bits 7 and 6 are not used and set to logic 0. example: configuration register 11 address (2ch) a/d cal pos register bits 0 - 7 this 8-bit control register contains a binary value used for positive increment for the level adjusting circuit of the a/d reference. the larger the step the faster the level reaches saturation. configuration register 12 address (30h) a/d cal neg register bits 0 - 7 this 8-bit control register contains a binary value used for the negative increment for the level adjusting reference of the a/d. the number is programmed as 256 - the value wanted since it is a negative number. configuration register 13 address (34h) tx spread sequence (high) bits 0 - 7 this 8-bit register is programmed with the upper byte of the transmit spreading code. this code is used for both the i and q signalling paths of the transmitter. this register combined with the lower byte tx_spread(low) generates a transmit spreading code programmable up to 16 bits. code lengths permitted are 11, 13, 15, and 16. right justified msb first. configuration register 9 address (24h) i/o definition register bits (0:7) range rssi_stat 7 6 5 4 3 2 1 0 0 0 0 0 0 0 0 0 00h (min) 0 0 1 1 1 1 1 1 3fh (max)
32 hsp3824 configuration register 14 address (38h) tx spread sequence (low) bits 0 - 7 this 8-bit register is programmed with the lower byte of the transmit spreading code. this code is used for the i and q signalling paths of the transmitter. this register combined with the higher byte tx_spread(high) generates the transmit spreading code programmable up to 16 bits. the example below illustrates the bit positioning for one of the 11 bit barker pn codes. example: configuration register 15 address (3ch) scrambler seed bits 0 - 7 this register contains the 7-bit (seed) value for the transmit scrambler which is used to preset the transmit scrambler to a known starting state. the msb bit position (7) is unused and must be programmed to a logic 0. the example below illustrates the bit positioning of seed. configuration register 16 address (40h) scrambler tap bits 0 - 7 this register is used to configure the transmit scrambler with a 7-bit polynomial tap configuration. the transmit scram- bler is a 7-bit shift register, with 7 configurable taps. a logic 1 is the respective bit position enables that particular tap. the msb bit 7 is not used and it is set to a logic 0. the example below illustrates the register configuration for the polynomial f(x) = 1 + x -4 +x -7 . each clock is a shift left configuration register 17 address (44h)cca timer threshold bits 0 - 7 this 8-bit register is used to configure the period of the time-out threshold of the cca watchdog timer. if the channel is busy the timer counts until it reaches the programmed value and at that point it declares that the channel is clear independent of the actual energy measured within the channel. this register is programmable up to 8 bits. for example, for a chip rate of 11 mcps and a desired timeout of ~11ms, n = 2ch. configuration register 18 address (48h) cca cycle threshold bits 0 - 7 this 8-bit register is used to configure how many times the cca timer is allowed to reach its maximum count before the channel is declared clear for transmission independent of the actual energy in the channel. this is an outer counter loop of the cca timer. each increment represents a time out of the cca timer. use a value of 03h for a time out of 2 cca timer counts. transmit spreading code 11-bit barker word right justified msb first. msb lsb tx_spread(high) 15 14 13 12 11 10 9 8 tx_spread(low) 7 6 5 4 3 2 1 0 11-bit barker code x x x x x 1 0 1 1 0 1 1 1 0 0 0 lsb bits (0:7) 7 6 5 4 3 2 1 0 xz -7 z -6 z -5 z -4 z -3 z -2 z -1 scrambler taps f(x) = 1 + x -4 +x -7 0 1 0 0 1 0 0 0 time (ms) 1000 n 5632 chip rate -------------------------- , where n is the programmable value of cr17. = lsb bits (0:7) 7 6 5 4 3 2 1 0 0 0 0 0 0 0 1 0 02h (min) cca_timer_th 1 1 1 1 1 1 1 1 ffh (max) msb lsb bits (0:7) 7 6 5 4 3 2 1 0 0 0 0 0 0 0 1 0 2h; 1 cca timer (min) cca_timer_th 1 1 1 1 1 1 1 1 ffh; 256 cca timer (max)
33 hsp3824 configuration register 19 address (4ch) rssi threshold, energy detect bits 0 - 7 this register contains the value for the rssi threshold for measuring and generating energy detect (ed). when the rssi exceeds the threshold ed is declared. ed indicates the presence of energy in the channel. the threshold that activates ed is programmable. bits 7 an 6 of this register are not used and set to logic 0. configuration register 20 address (50h) rx spread sequence (high) bits 0 - 7 this 8-bit register is programmed with the upper byte of the receive despreading code. this code is used for both the i and q signalling paths of the receiver. this register combined with the lower byte rx_spred(low) generates a receive despreading code programmable up to 16 bits. right justified msb first. see address 13 and 14 for example. configuration register 21 address (54h) rx spread sequence (low) bits 0 - 7 this 8-bit register is programmed with the lower byte of the receiver despreading code. this code is used for both the i and q signalling paths of the receiver. this register combined with the upper byte rx_spred(high) generates a receive despreading code programmable up to 16 bits. configuration register 22 address (58h) rx signal quality 1 acq (high) threshold bits 0 - 7 this control register contains the upper byte bits (8 - 14) of the bit sync amplitude signal quality threshold used for acquisition. this register combined with the lower byte represents a 15-bit threshold value for the bit sync amplitude signal quality measurements made during acquisition at each antenna dwell. this threshold comparison is added with the sq2 threshold in registers 30 and 31 for acquisition. a lower value on this threshold will increase the probability of detection and the probability of false alarm. set the threshold according to instructions in the text. configuration register 23 address (5ch) rx signal quality 1 acq threshold (low) bits 0 - 7 this control register contains the lower byte bits (0 - 7) of the bit sync amplitude signal quality threshold used for ac- quisition. this register combined with the upper byte represents a 15-bit threshold value for the bit sync amplitude sig- nal quality measurement made during acquisition at each antenna dwell. configuration register 24 address (60h) rx signal quality 1 acq read (high) bits 0 - 7 this status register contains the upper byte bits (8 - 14) of the measured signal quality threshold for the bit sync am- plitude used for acquisition. this register combined with the lower byte represents a 15-bit value, representing the mea- sured bit sync amplitude. this measurement is made at each antenna dwell and is the result of the best antenna. configuration register 25 address (64h) rx signal quality 1 acq read (low) bits 0 - 7 this register contains the lower byte bits (0 - 7) of the measured signal quality threshold for the bit sync amplitude used for acquisition. this register combined with the higher byte represents a 15-bit value, of the measured bit sync ampli- tude. this measurement is made at each antenna dwell and is the result of the best antenna. configuration register 26 address (68h) rx signal quality 1 data threshold (high) bits 0 - 7 this control register contains the upper byte bits (8-14) of the bit sync amplitude signal quality threshold used for drop lock decisions. this register combined with the lower byte represents a 15-bit threshold value for the bit sync amplitude signal quality measurements, made every 128 symbols. these thresholds set the drop lock probability. a higher value will increase the probability of dropping lock. configuration register address 27 (6ch) rx signal quality 1 data threshold (low) bits 0 - 7 this control register contains the lower byte bits (0 - 7) of the bit sync amplitude signal quality threshold used for drop lock decisions. this register combined with the upper byte represents a 15-bit threshold value for the bit sync amplitude signal quality measurements, made every 128 symbols. msb lsb bits (0:7) 7 6 5 4 3 2 1 0 0 0 0 0 0 0 0 0 00h (min) rssi_stat 0 0 1 1 1 1 1 1 3fh (max)
34 hsp3824 configuration register 28 address (70h) rx signal quality 1 data (high) threshold read (high) bits 0 - 7 this status register contains the upper byte bits (8-14) of the measured signal quality of bit sync amplitude used for drop lock decisions. this register combined with the lower byte represents a 15-bit value, representing the measured signal quality for the bit sync amplitude. this measurement is made every 128 symbols. configuration register 29 address (74h) rx signal quality 1 data threshold read (low) bits 0 - 7 this register contains the lower byte bits (0-7) of the measured signal quality of bit sync amplitude used for drop lock decisions. this register combined with the lower byte represents a 16-bit value, representing the measured signal qual- ity for the bit sync amplitude. this measurement is made every 128 symbols. configuration register 30 address (78h) rx signal quality 2 acq threshold (high) bits 0 - 7 this control register contains the upper byte bits (8-15) of the carrier phase variance threshold used for acquisition. this register combined with the lower byte represents a 16-bit threshold value for carrier phase variance measurement made during acquisition at each antenna dwell and is based on the choice of the best antenna. this threshold is used with the bit sync threshold in registers 22 and 23 to declare acquisition. a higher value in this threshold will increase the probability of acquisition and false alarm. configuration register 31 address (7ch) rx signal quality 2 acq threshold (low) bits 0 - 7 this control register contains the lower byte bits (0-7) of the carrier phase variance threshold used for acquisition. configuration register 32 address (80h) rx signal quality 2 acq read (high) bits 0 - 7 this status register contains the upper byte bits (8-15) of the measured signal quality of the carrier phase variance used for acquisition. this register combined with the lower byte generates a 16-bit value, representing the measured signal quality of the carrier phase variance. this measurement is made during acquisition at each antenna dwell and is based on the selected best antenna. configuration register 33 address (84h) rx signal quality 2 acq read (low) bits 0 - 7 this status register contains the lower byte bits (0-7) of the measured signal quality of the carrier phase variance used for acquisition. this register combined with the lower byte generates a 16-bit value, representing the measured signal quality of the carrier phase variance. this measurement is made during acquisition at each antenna dwell and is based on the selected best antenna configuration register 34 address (88h) rx signal quality 2 data threshold (high) bits 0-7 this control register contains the upper byte bits (8-15) of the carrier phase variance threshold. this register combined with the lower byte represents a 16-bit threshold value for the carrier phase variance signal quality measurements made every 128 symbols. configuration register 35 address (8ch) rx signal quality 2 data threshold (low) bits 0-7 this control register contains the lower byte bits (0-7) of the carrier phase variance threshold. this register combined with the upper byte) represents a 16-bit threshold value for the carrier phase variance signal quality measurements made every 128 symbols. configuration register 36 address (90h) rx signal quality 2 data read (high) bits 0-7 this status register contains the upper byte bits (8-15) of the measured signal quality of the carrier phase variance. this register combined with the lower byte represents a 16-bit value, of the measured carrier phase variance. this measurement is made every 128 symbols. configuration register 37 address (94h) rx signal quality 2 data read (low) bits 0-7 this register contains the lower byte bits (0-7) of the measured signal quality of the carrier phase variance. this register combined with the represents a 16-bit value, of the measured carrier phase variance. this measurement is made every 128 symbols. configuration register address 38 (98h) rx signal quality 8-bit read bits 0 - 7 this 8-bit register contains the bit sync amplitude signal quality measurement derived from the 16-bit bit sync signal quality value stored in the cr28-29 registers. this value is the result of the signal quality measurement for the best antenna dwell. the signal quality measurement provides 256 levels of signal to noise measurement.
35 hsp3824 configuration register 39 address reserved reserved configuration register 40 address reserved reserved configuration register 41 address (a4h) sfd search time bits 0 - 7 this register is programmed with an 8-bit value which represents the length of time for the demodulator to search for a sfd in a receive header. each bit increment represents 1 symbol period. configuration register 42 address (a8h) dsbpsk signal bits 0 - 7 this register contains an 8-bit value indicating the data packet modulation is dbpsk. this value will be a oah for full protocol operation at a data rate of 1 mbps, and is used in the transmitted signalling field of the header. this value will also be used for detecting the modulation type on the received header. configuration register 43 address (ach) dqpsk signal bits 0 - 7 this register contains the 8-bit value indicating the data packet modulation is dqpsk. this value will be a 14h for full protocol operation at a data rate of 2 mbps and is used in the transmitted signalling field of the header. this value will also be used for detecting the modulation type on the received header. configuration register 44 address (b0h) rx service field (reserved) bits 0 - 7 this register contains the detected received 8-bit value of the service field for the header. this field is reserved for the full protocol mode for future use and should be always a 00h. configuration register 45 address (b4h) rx data length (high) bits 0 - 7 this register contains the detected higher byte (bits 8-15) of the received length field contained in the header. this byte combined with the lower byte indicates the number of transmitted bits in the data packet. configuration register 46 address (b8h) rx data length (low) bits 0 - 7 this register contains the detected lower byte of the received length field contained in the header. this byte com- bined with the upper byte indicates the number of transmitted bits in the data packet. configuration register 47 address (bch) rx crc16 (high) bits 0 - 7 this register contains the upper byte bits (8 -15) of the received crc16 field header. this register combined with the lower byte represents a 16-bit crc16 value protecting transmitted header. the fields protected are selected by con- figuring the header control bits at configuration register 2. configuration register 48 address (c0h) rx crc16 (low) bits 0 - 7 this register contains the lower byte bits (0-7) of the received crc16 field header. this register combined with the upper byte represents a 16-bit crc16 value protecting transmitted header. the fields protected are selected by con- figuring the header control bits at configuration register 2. msb lsb rx_crc16 15 14 13 12 11 10 9 8 7 6 5 4 3 2 1 0 rx_crc16(high) 76543210 rx_crc16(low) 7 6 5 4 3 2 1 0 note: the receive crc16 field protects the following ?elds depending upon the mode selection, as de?ned in configuration register 2. mode 0 crc16 not used mode 1 crc16 protects sfd mode 2 crc16 protects sfd, and length field mode 3 crc16 protects signalling field, service field, and length field
36 hsp3824 configuration register 49 address (c4h) sfd (high) bits 0 - 7 this 8-bit register contains the upper byte bits (8-15) of the sfd used for both the transmit and receive header. this register combined with the lower byte represents the 16-bit value for the sfd field. configuration register 50 address (c8h) sfd (low) bits 0 - 7 this 8-bit register contains the upper byte bits (0-7) of the sfd used for both the transmit and receive header. this register combined with the lower byte represents the 16-bit value for the sfd field. configuration register 51 address (cch) tx service field bits 0 - 7 this 8-bit register is programmed with the 8-bit value of the service field to be transmitted in a header. this field is reserved for future use and should be always a 00h. configuration register 52 address (d0h) tx data length field (high) bits 0 - 7 this 8-bit register contains the higher byte (bits 8-15) of the transmit length field described in the header. this byte combined with the lower byte indicates the number of bits to be transmitted in the data packet. cr 52/53 should not be set to 0000h. this value would cause the modem to reset after sfd. configuration register 53 address (d4h) tx data length field (low) bits 0 - 7 this 8-bit register contains the lower byte bits (0-7) of the transmit length field described in the header. this byte combined with the higher byte indicates the number of bits to be transmitted in the data packet, including the mac payload header. cr 52/53 should not be set to 0000h. this value would cause the modem to reset after sfd. configuration register 54 address (d8h) tx crc16 (high) bits 0 - 7 this 8-bit register contains the upper byte (bits 8-15) of the transmitted crc16 field for the header. this register combined with the lower byte represents a 16-bit crc16 value calculated by the hsp3824 to protect the transmitted header. the fields protected are selected by configuring the header mode control bits at register address 02. configuration register 55 address (dch) tx crc16 (low) bits 0 - 7 this 8-bit register contains the lower byte (bits 0-7) of the transmitted crc16 field for the header. this register com- bined with the higher byte represents a 16-bit crc16 value calculated by the hsp3824 to protect the transmitted header. the fields protected are selected by configuring the header mode control bits at register address 02. configuration register 2 configuration register 56 address (e0h) tx preamble length bits 0 - 7 this register contains the count for the preamble length counter. this counter is programmable up to 8 bits and rep- resents the number of preamble bits. this should be set at 50h for 1 antenna and 80h for dual antennas. msb lsb rx_crc16 15 14 13 12 11 10 9 8 7 6 5 4 3 2 1 0 rx_crc16(high) 7 6 5 4 3 2 1 0 rx_crc16(low) 7 6 5 4 3 2 1 0 note: the receive crc16 field protects the following ?elds depending upon the mode selection. as de?ned in register address 02. mode 0 crc16 not used mode 1 crc16 protects sfd mode 2 crc16 protects sfd, and length field mode 3 crc16 protects signalling field, service field, and length field
37 speci?cations hsp3824 at 33mhz absolute maximum ratings reliability information supply voltage . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 7.0v input, output or i/o voltage . . . . . . . . . . . . gnd -0.5v to v cc +0.5v storage temperature range . . . . . . . . . . . . . . . . . -65 o c to +150 o c junction temperature . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 150 o c lead temperature (soldering 10s) (lead tips only) . . . . . . +300 o c esd classi?cation . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . class 1 thermal resistance (typical) q ja tqfp package . . . . . . . . . . . . . . . . . . . . . . . . . . . . 80 o c/w package power dissipation at 85 o c tqfp package . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 0.81w gate count . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 25,000 gates caution: stresses above those listed in absolute maximum ratings may cause permanent damage to the device. this is a stress only rating and operation of the device at these or any other conditions above those indicated in the operational sections of this speci?cation is not implied. operating conditions operating voltage range . . . . . . . . . . . . . . . . . . . +2.70v to +5.50v operating temperature range . . . . . . . . . . . . . . . . . -40 o c to +85 o c dc electrical speci?cations v cc = 3.0v to 5.0v 10%, t a = -40 o to +85 o c parameter symbol test conditions min typ max units power supply current i ccop v cc = max, clk frequency 22mhz (notes 1, 2) -6977ma standby power supply current i ccsb v cc = max, outputs not loaded - 1 2.5 ma input leakage current i i v cc = max, input = 0v or v cc -10 1 10 m a output leakage current i o v cc = max, input = 0v or v cc -10 1 10 m a logical one input voltage v ih v cc = max, min 0.7 v cc -v logical zero input voltage v il v cc = min, max - v cc /3 v logical one output voltage v oh i oh = -1ma, v cc = min v cc -0.4 v cc -.2 - v logical zero output voltage v ol i ol = 2ma, v cc = min - .2 0.4 v input capacitance c in clk frequency 1mhz all measurements referenced to gnd. t a = +25 o c, note 2 - 5 10 pf output capacitance c out - 5 10 pf notes: 1. output load 30pf. i ccop = 5.5 + 4.7(v) + 3.7e - 7 (v)(f); v = volts, f = freq. example: 5.5 + 4.7(5.5) + 3.7e - 7(5.5)(22e6) = 77 2. not tested, but characterized at initial design and at major process/design changes. ac electrical speci?cations v cc = 3.0v to 5.0v 10%, t a = -40 o to +85 o , (note 1) parameter symbol 33mhz units min max clk period (mclk) t cp 30 - ns clk high (mclk) t ch 9-ns clk low (mclk) t cl 9-ns setup time to mclk (txd) t s2 10 - ns hold time from mclk (txd) t h2 20 - ns sclk clock period t p 100ns or mclk - ns sclk high t h 20 - ns sclk low t l 20 - ns set up to sclk (sd, as, r/ w, cs) t s1 20 - ns hold time from sclk (sd, as, r/ w, cs) t h1 20 - ns sd out from sclk t d1 -30ns output enable of sd from r/ w high t e1 - 20 ns (note 2) output disable of sd after r/ w low t f1 - 20 ns (note2) txclk, txrdy, i, q from mclk t d2 -35ns rxclk, md_rdy, rxd from mclk t d3 -35ns test 0-7, cca, agc, from mclk t d4 -40ns anstel, test_ck ---- output rise/fall - 10 ns (note 2, 3) notes: 1. ac tests performed with c l = 40pf, i ol = 2ma, and i oh = -1ma. input reference level all inputs 1.5v. test v ih = v cc , v il = 0v; v oh = v ol = v cc /2. 2. not tested, but characterized at initial design and at major process/design changes. 3. measured from v il to v ih .
38 speci?cations hsp3824 i and q a/d ac electrical speci?cations parameter min typ max units full scale input voltage (v p-p ) 0.25 0.50 1.0 v input bandwidth (-0.5db) - 20 - mhz input capacitance - 5 - pf input impedance (dc) 5 - - k w fs (sampling frequency) - - 44 mhz rssi a/d electrical speci?cations parameter min typ max units full scale input voltage (v p-p ) - - 1.15 v input bandwidth (0.5db) 1mhz - - mhz input capacitance (dc) - 7pf - pf input impedance 1m - - m w
39 speci?cations hsp3824 at 44mhz test circuit notes: 1. includes stray and jig capacitance 2. switch s1 open for i ccsb and i ccop figure 22. test load circuit absolute maximum ratings reliability information supply voltage . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 7.0v input, output or i/o voltage . . . . . . . . . . . . gnd -0.5v to v cc +0.5v storage temperature range . . . . . . . . . . . . . . . . . -65 o c to +150 o c junction temperature . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 150 o c lead temperature (soldering 10s) (lead tips only) . . . . . . +300 o c esd classi?cation . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . class 1 thermal resistance (typical) q ja tqfp package . . . . . . . . . . . . . . . . . . . . . . . . . . . . 80 o c/w package power dissipation at 85 o c tqfp package . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 0.81w gate count . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 25,000 gates caution: stresses above those listed in absolute maximum ratings may cause permanent damage to the device. this is a stress only rating and operation of the device at these or any other conditions above those indicated in the operational sections of this speci?cation is not implied. operating conditions operating voltage range . . . . . . . . . . . . . . . . . . . . . +3.3v to +5.0v operating temperature range . . . . . . . . . . . . . . . . . -40 o c to +85 o c dc electrical speci?cations v cc = 3.3v to 5.0v t a = -40 o to +85 o c parameter symbol test conditions min typ max units power supply current i ccop v cc = max, clk frequency 44mhz (notes 1, 2) - 105 111 ma see previous dc table for remaining dc specifications notes: 4. output load 30pf, i ccop = 5.5 + 4.7(v) + 3.7e - 7 (v)(f); v = volts, f = freq. example: 5.5 + 4.7(5.0) + 3.7e - 7(5.0)(44e6) = 111 5. not tested, but characterized at initial design and major process/design changes. ac electrical speci?cations v cc = 3.3v to 5.0v, t a = -40 o to +85 o , (note 1) parameter symbol 44mhz units min max clk period (mclk) t cp 22.5 - ns clk high (mclk) t ch 9-ns clk low (mclk) t cl 9-ns txclk, txrdy, i, q from mclk t d2 -25ns rxclk, md_rdy, rxd from mclk t d3 -25ns test 0-7, cca, agc, from mclk t d4 -27ns anstel, test_ck ---- see previous ac table for remaining ac specifications notes: 1. ac tests performed with c l = 40pf, i ol = 2ma, and i oh = -1ma. input reference level all inputs 1.5v. test v ih = vcc, v il = 0v; v oh = v ol = v cc /2. equivalent circuit c l ioh 1.5v iol dut s 1 (note 2) (note 1)
40 hsp3824 waveforms figure 23. serial control port signal timing figure 24. tx port signal timing note: rxd is output one mclk after rxclk rising to provide data hold time. figure 25. rx port signal timing figure 26. miscellaneous signal timing t p t s1 t h1 t d1 t e1 t f1 sclk sd, as, r/ w, cs sd (as output) r/ w sd t h t l t cp t cl t ch t d2 t d2 t s2 t h2 txd txrdy, i, q txclk mclk t d3 t d3 t d3 mclk rxclk md_rdy rxd t d4 mclk test 0-7, agc, cca, antsel, test_ck
41 hsp3824 d d1 e e1 -a- pin 1 a2 a1 a 11 o -13 o 11 o -13 o 0 o -7 o 0.020 0.008 min l 0 o min plane b 0.004/0.008 0.09/0.20 with plating base metal seating 0.004/0.006 0.09/0.16 b1 -b- e 0.003 0.08 a-b s d s c m 0.08 0.003 -c- -d- -h- 0.25 0.010 gage plane thin plastic quad flatpack packages (tqfp) 1 q48.7x7 (jedec mo-136ae issue c) 48 lead thin plastic quad flatpack package symbol inches millimeters notes min max min max a - 0.047 - 1.20 - a1 0.002 0.005 0.05 0.15 - a2 0.038 0.041 0.95 1.05 - b 0.007 0.010 0.17 0.27 6 b1 0.007 0.009 0.17 0.23 - d 0.347 0.362 8.80 9.20 3 d1 0.268 0.283 6.80 7.20 4, 5 e 0.347 0.362 8.80 9.20 3 e1 0.268 0.283 6.80 7.20 4, 5 l 0.018 0.029 0.45 0.75 - n48 487 e 0.020 bsc 0.50 bsc - rev. 0 4/95 notes: 1. controlling dimension: millimeter. converted inch dimensions are not necessarily exact. 2. all dimensions and tolerances per ansi y14.5m-1982. 3. dimensions d and e to be determined at seating plane . 4. dimensions d1 and e1 to be determined at datum plane . 5. dimensions d1 and e1 do not include mold protrusion. allowable protrusion is 0.25mm (0.010 inch) per side. 6. dimension b does not include dambar protrusion. allowable dambar protrusion shall not cause the lead width to exceed the maximum b dimension by more than 0.08mm (0.003 inch). 7. n is the number of terminal positions. -c- -h-

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